Analog and RF circuit techniques in nanometer CMOS · 2016. 2. 17. · b.nauta@utwente .nl...
Transcript of Analog and RF circuit techniques in nanometer CMOS · 2016. 2. 17. · b.nauta@utwente .nl...
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Analog and RF circuit techniques in nanometer CMOS
Bram Nauta University of Twente
The Netherlands http://icd.ewi.utwente.nl
b.nauta@utwente .nl
UNIVERSITY OF TWENTE.
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Outline
• Introduction • Balun-LNA-Mixer (BLIXER) • Interferer robust SDR RX – analog part • Interferer robust SDR RX – digital part • Summary
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ωLO
ωLO
Preferred: one wide band frontend IC: Software Defined
Keep minimal
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RF system trend (I)
• Challenges wide band circuits:
Minimal pre-filtering: high linearity No high Q tanks: low noise • Bandwidth will be ok for low GHz
• Towards Software Defined Radio
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Outline
• Introduction • Balun-LNA-Mixer (BLIXER) • Interferer robust SDR RX – analog part • Interferer robust SDR RX – digital part • Summary
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BLIXER
Balun + LNA + Mixer
[Blaakmeer, ISSCC2008]
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ωLO
ωLO
BLIXER=Wide band receiver
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Balun-LNA Simultaneous: • Single-to-Differential • Balanced Gain • Broadband input
match ( ~1/gmCG ) • Noise Canceling • Distortion Canceling
[Blaakmeer et al. ESSCIRC `07]
RS vs
vin +
-
vout + -
CG CS
IBias
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Noise Canceling
vin +
- Ibias
in
50Ω
20mS
80mS
200Ω 50Ω
vs
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10 10
Bandwidth problem:
vin +
- Ibias
50Ω
20mS
80mS
200Ω 50Ω
vs
C < 80fF for BW=10GHz
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So, Don’t make voltage gain @ RF
vin +
- Ibias
50Ω
20mS
80mS
200Ω 50Ω
vs
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12 12
Use a MIXER
vin +
- Ibias
50Ω
20mS
80mS
200Ω 50Ω
vs
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RS vs
RF: no high-Z nodes
Now Low frequency
Low-Z
LO
gm
4·gm
Z 4·Z
IBias
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Mixer stacked on CG-CS stage
gm·vrf 4·gm·vrf
vs
RS
W 4·W
IF+ IF-
LO+ LO-
Z 4·Z
R
3·R
3·C
C
vrf + -
‘CG’ ‘CS
’
[Blaakmeer, ISSCC’08]
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Chip Micrograph and PCB detail
Baseline 65nm CMOS 1.2V supply Active area < 0.02 mm2
OSC
IN IF Out Lbias
OSC
IN
IF I+ IF I-
IF Q+ IF Q-
Supply & Biasing
LO gen + buf Core + IF-buf Biasing
1.4 mm
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Conversion Gain, NF and S11
16 RX-frequency [GHz]1 10
[dB]
-30
-20
-10
0
10
20GC
NF
S11 fIF = 50 MHz
7GHZ
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Other BLIXER Performance
• Linearity: – IIP3 @ RF: -3 dBm – IIP2 @ RF: +20 dBm
• Quadrature accuracy: – Phase error < 3° – Gain error < 1dB
• LO leakage < -50 dBm • Dissipation
– 33mW (LO=500MHz) – 57mW (LO=7GHz)
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Outline
• Introduction • Balun-LNA-Mixer (BLIXER) • Interferer robust SDR RX – analog part • Interferer robust SDR RX – digital part • Summary
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A Software-Defined Radio Receiver Architecture
Robust to Out-of-Band Interference
[Ru, ISSCC 2009]
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ωLO
ωLO
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Conventional Multi-Band Receiver
• RF filters for out-of-band interference, but bulky, costly, lossy, inflexible… • Our goal: Software Defined Radio with relaxed RF filtering
…
Chip
850M
900MLNA
LNA
LNA
LNA
Ante
nna
Switc
hes
IFA
LPF
IFA
LPF1800M
1900M
0/90° LO
…
!
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Wideband Interfering: Nonlinearity
• Wideband LNA: also amplifies interference à nonlinearity
-50dBm
+10dBm
0.8G 1.6G 2.4G
-20dBm
3.2G
-70dBm-10dBm
0.8G 1.6G
Wanted Interference
2.4G
-40dBm
LNAA B C 0.8G 2.4G
...WidebandGain=20dB
Intermodulation & blocking
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Wideband Interfering: Harmonic Mixing
• Switching mixer: square-wave LO à harmonic mixing
LNAA B C 0.8G 2.4G
...WidebandGain=20dB
-70dBm -40dBm
0.8G 2.4G
-50dBm
DC
-30dBm-50dBm-20dBm
0.8G 2.4G
Wanted 3rd harmonic
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Concept: Use LP Filtering for Selectivity
• Voltage gain only at BB after low-pass filter (LPF) to filter blockers à Keep low impedance over a wide band at node B
V-IA B C
I-V
LO
LNA1st node with voltage gain
Baseband (BB)
RFLPF
50Ω
Low Gain,Low Pain.
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Realization: Wideband LNTA + Mixer + TIA
• LNTA: high Gm & high Rout à low noise small voltage swing at node B à good linearity • Similar to [1], but now wideband and with blocker filtering
[1] Redman-White & Leenaerts, ESSCIRC07
LNTAA B C
OTAD
LO
RF BB50Ω
Impe
danc
e
f
≈+Rmixer
DCLO f
V-I LPF & I-V
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Harmonic Rejection (HR) Mixer: Remove 3LO and 5LO
[2] Weldon et. al., ISSCC01
45°
1
1√2
3rd or 5th harmonic
: cancel!
√245°
1
1
1st or 7th harmonic
: add up!
• Amplitude weighting + phase shifting à emulate sine-LO
ÞLO3
LO2
LO1
x1
x√2
x1
Effective LO
1RF BB
Û
LO1
1
1
LO2
LO3
√2RF BB
-45°
0°
45°
1
1√2
Þ
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Problem: Amplitude and Phase Errors
• Amplitude and phase errors à unwanted harmonic residue à degrade HR ratio • How to make irrational ratio, e.g. √2, on chip?
3rd or 5th harmonic vector diagram
Phase Error45°
1
1 √2
Δφ
residue
Amplitude Error45°
1
1 √2(1+α)residue
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2-Stage Polyphase HR: Concept
• 41/29=1.4138, √2=1.4142 à ε=0.03%
1st Stage 2nd Stage
2
23
2
23
x2x3x2
x2x3x2
x2x3x2
0°
45°
-45°
0°45°90°
135°
45°90°
2
23
x7
x5
x5
29
2941
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2-Stage Polyphase HR: Realization
• RF LNTA for 1st-stage weighting (2:3:2) • BB resistor for 2nd-stage weighting (5:7:5) • Nominally √2, what about influence of mismatch?
-+-+
-+-+
-+-+
-+-+
0°
45°
90°
135°
180°
225°
270°
315°
2Gm
2Gm
3GmRF+-
50Ω
50Ω Q+
-
-+-+
-+-+
I+
-
75
7
75
7
75
7
75
7LNTA
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Reduced Effect of Amplitude Mismatch
• 2-stage polyphase à product of relative errors • E.g. 2:3:2 à α=6% à 1st-stage only: HR3=40dB 5:7:5 à β=1% à 2-stage total: HR3=86dB
3rd or 5th harmonic
1st
harmonic(desired signal)
45°
√2α·1
√2α·√2(1+β)
2αβ
√2α·1
√2(2+α)·√2(1+β)
2(2+α)(2+β)45°
√2(2+α)·1
√2(2+α)·1
2nd stage (error β in √2)
≈ratio α2 ·β2≈ratio
α2
45°
1
1√2(1+α)
√2α
√2(1+α)
√2(2+α)45°
1
1
1st stage (error α in √2)
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• LP blocker filtering: attenuates interference around LO • 2-stage polyphase HR: robustly attenuates 3LO and 5LO
RF Filtering is Relaxed!
50ΩLNTARF BB
2:3:2 HR Mixer 757
OTA OTA
RF to BB Periodic Transfer Funciton (PXF)
LO 3LO 5LO 7LO fDC
17dBPXF (dB)
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Zero-IF Receiver Prototype
2Gm
2Gm
3Gm
-+-+
-+-+
-+-+
-+-+
RF+-
Chip
Q+
-
8
-+-+
-+-+
I+
-
8CLK+-
50Ω
50Ω
100Ω
757
Clock
LNTA Mixer
TIA1
757
757
757
R-net
TIA2
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Chip Photo
• 1mm2 in 65nm CMOS
• VDD: 1.2V • Current
consumption: – Analog 33mA – Digital 17mA
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Measured HR: 40 Chips
• No trimming & calibration, no RF filtering
Min. HR3=60dBMin. HR5=64dB
10 20 30 401
60
70
80
90
Sample #
HR
Rat
io (d
B)HR Ratio @ 0.8G LO
5th3rd
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Measured Performance Summary
VDD 1.2V Current
Consumption Analog: 33mA Digital (clock):
8mA @ 0.4GHz 17mA @ 0.9GHz
1 Out-of-band IIP3: two tones = 1.61G & 2.40GHz, LO = 819MHz 2 Out-of-band IIP2: two tones = 1.80G & 2.40GHz, LO = 601MHz
LO Frequency 0.4~0.9GHz Gain 34.4±0.2dB
DSB NF 4dB±0.5dB S11 < -10dB 80M~5.5GHz
In/Out-of-band IIP31
+3dBm / +18dBm
In/Out-of-band IIP22
+46dBm / +51dBm
IF Bandwidth 12MHz 1/f noise 30kHz corner
Harmonic Rejection Ratio @ 0.8GHz LO
3rd-order > 60dB (40 chips) 5th-order > 64dB (40 chips)
2nd, 4th, 6th > 62dB (20 chips)
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Conclusion: A SDR Receiver Architecture
Robust to Out-of-Band Interference
• Only voltage gain @ BB after low-pass filtering – In-band IIP3 +3dBm & out-of-band IIP3 +18dBm
• 2-stage polyphase harmonic rejection technique – Robust: error = product of errors – Accurate multiphase clock – Minimum HR 60dB over 40 chips without
calibration / trimming / RF filters
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Outline
• Introduction • Balun-LNA-Mixer (BLIXER) • Interferer robust SDR RX – analog part • Interferer robust SDR RX – digital part • Summary
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The Digital approach:
Harmonic Rejection Exploiting Adaptive
Interference Cancellation
[Moseley, ISSCC 2009]
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Harmonic Rejection RX: This work
ADC
ADC
ADC
ADC
x0
x45
x90
x135
2Gm
2Gm
3Gm
-+-+
-+-+
-+-+
-+-+
RF+-
Chip
8
8CLK+-
50Ω
50Ω
100Ω
To Digital Harmonic Rejection Algorithm
(Baseband processor)
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The Basic Idea
Subtract interference (residual harmonic image responses)
from received signal.
• Need interference estimate signal.
-Interference
Estimate
Desired Signal+ Interference Desired Signal
d(n)
v(n)
e(n)
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Adaptive Interference Cancelling (AIC)
• Adaptive “filter” aligns phase & amplitude. • Minimizes cross-correlation v(n) and e(n).
Digital“Filter”
-Interference
Estimate
Desired Signal+ Interference Desired Signal
LearningAlgorithmFilter Coefficients
w(n)
r(n)
v(n)
e(n)
y(n)
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Two I/Q signals
ADC
ADC
ADC
ADC
x0
x45
x90
x135
2Gm
2Gm
3Gm
-+-
+
-+-
+
-+-
+
-+-
+
RF+-
Chip
8
8CLK+-
50Ω
50Ω
100Ω
r(n) = x0 + j·x90
IQ2(n) = x45 + j·x135
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Interference estimate
r(n) IQ2 IQ’2 v(n)=r(n)-IQ’2Desired signal
3rd harmonicresponse
r(n) IQ2 IQ’2 v(n)=r(n)-IQ’2
5th harmonicresponse
r(n) IQ2 IQ’2 v(n)=r(n)-IQ’2
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AIC Algorithm 1/5
RF Input
ADC
ADC
ADC
ADC
j
j
-45°
(.)*
w1* w2*
- -r(n)
v(n)
e(n)
LMSupdate
x0
x45
x90
x135
IQ1
IQ2
Adaptive Interference Canceller
To Rest ofBaseband Processing
Master Clock
ANALOG
FRONT
END
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AIC Algorithm 2/5
RF Input
ADC
ADC
ADC
ADC
j
j
-45°
(.)*
w1* w2*
- -r(n)
v(n)
e(n)
LMSupdate
x0
x45
x90
x135
IQ1
IQ2
Adaptive Interference Canceller
To Rest ofBaseband Processing
Master Clock
ANALOG
FRONT
END
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AIC Algorithm 3/5
RF Input
ADC
ADC
ADC
ADC
j
j
-45°
(.)*
w1* w2*
- -r(n)
v(n)
e(n)
LMSupdate
x0
x45
x90
x135
IQ1
IQ2
Adaptive Interference Canceller
To Rest ofBaseband Processing
Master Clock
ANALOG
FRONT
END
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AIC Algorithm 4/5
RF Input
ADC
ADC
ADC
ADC
j
j
-45°
(.)*
w1* w2*
- -r(n)
v(n)
e(n)
LMSupdate
x0
x45
x90
x135
IQ1
IQ2
Adaptive Interference Canceller
To Rest ofBaseband Processing
Master Clock
ANALOG
FRONT
END
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AIC Algorithm 5/5
RF Input
ADC
ADC
ADC
ADC
j
j
-45°
(.)*
w1* w2*
- -r(n)
v(n)
e(n)
LMSupdate
x0
x45
x90
x135
IQ1
IQ2
Adaptive Interference Canceller
To Rest ofBaseband Processing
Master Clock
ANALOG
FRONT
END
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Demonstration
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Demonstration
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Demonstration
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Demonstration
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Demonstration
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Comparison
This work Z. Ru ISSCC 2009 12.8
Rej. strongest >80 dB (1) >60 dB
Rej. other odd >36 dB >60 dB
Rej. even >64 dB >62 dB
Power frontend 45 mA @ 1.2 V (excl. ADCs)
50 mA @ 1.2 V (excl. ADCs)
Power DSP (100 Msps)
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Adaptive Interference Cancellation: Conclusions
Dual-domain Harmonic Rejection Mixer (HRM) proposed: – Analog HRM + 4 ADCs + Digital AIC. – Strongest correlating harmonic image is removed – X-correlation -> independent of signal shape. – Stronger interferer -> more rejection
• Measurements: – First stage (analog) HR > 36 dB. – Dual domain HR3 or HR5 > 80 dB. – Limitation: even-order HR > 64 dB.
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Outline
• Introduction • Balun-LNA-Mixer (BLIXER) • Interferer robust SDR RX – analog part • Interferer robust SDR RX – digital part • Summary
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Summary
• BLIXER – Noise cancelling – no voltage gain @ RF
• Interferer robust RX – No voltage gain @ RF – Filter before voltage gain – HR: error of errors
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Summary
• Digital Harmonic Rejection RX – Adaptively kills the biggest harmonic interferer