[IEEE 2012 6th International Conference on Signal Processing and Communication Systems (ICSPCS 2012)...
Transcript of [IEEE 2012 6th International Conference on Signal Processing and Communication Systems (ICSPCS 2012)...
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Abstract— Thhen subjected gma (ΔΣ) upc
ven-quantisatiomprovement indd-quantisationhannel power (Ahe smaller firsoise for small sgnal is frequen
the spectrumontributor folletter noise perot improve thhen frequency
Currently, the evice plays aeveloping tech
WLAN, mobilequire more po
nd high bandwave high efficsing a pulse tulse position ffective for linivision Multipata rate commFDM suffers fat will limit th
onnectivity, inwards maintai
nd wide bandwAll nonlinear put waveform
uture generatiomethod towardower amplifiermportant technhich can be us
nd phase. PWmplitude and gnals are conte switched mgnals are gengnals must bWM/PPM sign
OFD
2Telecom3Sch
his paper studto OFDM in
converter. Theon method of [n performancen scheme haACP) comparest quantisationsignals, leadingncy offset, a num. The third hlowed by the rformance of the distortion s
offsetting is av
I. INTROcommunicatio
an essential rhnology of w
e 3G & 4G, anower efficienc
width. Switch ciency but thetrain for drivinmodulation (earity requiremplexing (OFD
munications in from high-peahe energy efficn order to obining spectral
width become vPA classes c
m (e.g. class Don of wireless ds high efficirs (RF-PAs) wnique in SMsed to generate
WM/PPM signaphase. The a
trolled by the mode output rnerated in Cabe convertednals.
DM Pe
Sirmaya1School of
mmunication hool of Innov
dies the odd-qunput signals ine results will [9] to establishe. The overall as about 5dBed to the even-
n step results ing to a lower n
umber of distorharmonic is th
image. Interethe odd-quantspectra. Best voided.
ODUCTION on connectivityrole in daily
wireless transmnd public digitcy, good lineamode power ae linearity is ng SMPAs w
(PWM/PPM) ment [3,4]. Or
DM) nowadayn multi-carrier ak-to-average pciency [5]. Thbtain higher efficiency, pe
very critical. can be operateD and E), resul
base stationsiency linear rwhich has been
MPA architecte an RF signalals are usuallyamplitude andpulse width a
respectively. Nartesian formad to Polar f
erformin Car
anti Sirmayanf EngineeringEngineeringvative Techn
E-mail:
uantisation techn a Cartesianbe compared
h whether therperformance
B reduced adquantisation scn lower quant
noise floor. Whrtions become he biggest distestingly, the otisation schemperformance
y through a wy life. The rmitters such tal broadcastinarity, high datamplifiers (SMvery critical
with pulse widin Cartesian
rthogonal Freqys can suppor
systems. Howpower ratio (P
herefore, for wdata rates, dierformance lin
ed with a swilting in SMPA. This is a poradio frequenn proposed [2ture is PWMl with any ampy quantized ind phase of th
and pulse positNormally, basat. Therefore, format to ge
mance wrtesiannti1,2, Vandang and Scienc
g Study Progrnologies and {sirmayanti
hnique
n Delta to the e is an of the
djacent cheme. tisation hen the
visible tortion overall
me does occurs
wireless rapidly as for
ng will ta rate
MPAs) [1,2].
dth and ΔΣ is
quency rt high wever, PAPR)
wireless irected nearity
itching A for a otential ncy of 2]. The M/PPM plitude n both he RF tion of seband
these enerate
Thgenpulsshapby subsFig.to comsign
Fig. phas
A
gensystevenformclocare twoquanthe
ThquanOddpulspha…) valurefesepa
In quanshoulargAccdistr
with On ΔΣ Una Bassoo3, He, Victoria Uram, the StateEngineering,.sirmayanti}
he authors in erate a binaryse position forpe the noise asubtracting thsequent sampl.1 was used toPWM/PPM’
mponents whenal is offset fro
1. Cartesian ΔΣse in odd-quantisa
novel all digierate a pulse ttem was propn-quantisationming the outpuck periods. Thcalculated by
o clock periodntisation at loweven-quantisa
his paper offntisation of [9d-quantisation sewidths by onse reference. Tfor the odd-q
ues for the eerence does narate quantiser
the followintisation will uld be noted t
ge signal dynacess (CDMA) ribution. Th
Odd-EUpconHorace King
University, Me Polytechnic, University o @live.vu.ed
[3,6] developy signal with r driving an SMaway from thehe current qule [7]. The Ca
o suppress the block can
en the carrierom its nominal
Σ Upconverters. Qation scheme.
ital approach wtrain for drivinosed in [9]. T
n technique wut is based onhe quantised ay changing thds. However, w signal level
ation scheme isfers an altern9] using a ne
was propone clock perioThe acceptablequantisation ceven-quantisatnot change wrs for amplituding, Cartesian
be considerethat most of toamics. OFDMare often mod
he signals mu
Even Qnverter
1, Mike FaulkMelbourne, Au
c of Ujung Pof Technolog
du.au
ped a Cartesian appropriat
MPA. ΔΣ techne band of inteuantised errorartesian ΔΣ tequantisation n
generate ur frequency ol frequency [8
QR and Q quant
with a quantisng an SMPA inThe proposed where the thren pulses with aamplitudes, e pulsewidthsthis leads to ls as the minims two clock penative approaew scheme ofosed to reduod while maine pulsewidths
compared to thtion. In both with the pulsde and phase. n ΔΣ upconved when apploday’s modulaM and Code deled with a Rust be backed
Quantirs kner1 ustralia
Pandang, Indogy, Mauritius
ian ΔΣ systeme pulse widthniques was use
erest. They opr signal fromechnique shownoise but the ‘Punwanted speof the transm,9].
tise the amplitud
sation techniqun the Cartesianquantiser use
ee-level-wavean even numb of the RF si
s in incremena potential co
mum pulsewideriods. ach to the ef odd-quantisauce the posntaining a conbecome (0, 1,he (0, 2, 4, 6
cases the psewidth, allow
verter with lied to OFDM
ation schemes Division Mul
Rayleigh amplid off so that
sation
onesia s
m to h and ed to erate
m the wn in Polar ectral
mitted
de and
ue to n ΔΣ
ed an form er of ignal
nts of oarse dth in
even-ation. ssible nstant , 3, 5 6 …) phase wing
odd-M. It have ltiple itude t the
n
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uantisation scmulation setupven-quantisatioraw a conclusio
II. ΔΣ filtering versampling aoise power spver a wider baBB) oversamoise proportioaseband is give
here is theampling frequhaped using function (NTF)
g. 2. Mod-2 Lowp
The comparisdd-quantisationuantisation scWM generatioThe PWM/PPversample theutput (fc) by a
The phase is tcrements over
etermined by tom the middulsewidths. Hven by
handle the pead probability ally, thereforerated at the lowon of this paperence caused b. We show thahemes producefrequency offsbacked-off (poe odd-quantisas organized ection II prescheme. Sectiop and results oon and odd-quon in section V
ODD QUANis achieve
and noise shaectral density
andwidth. As empling rate (Oonal to [7en by
e maximum uency. The qfeedback in thfor a lowpass
pass ΔΣ.
on between en schemes heme affects
on block ‘PolaPM process ree nominal RFfactor of OSR
therefore unifor the range 0 the pulse positdle of the puHowever the r
ak powers. Thof low signa
e, the quantisw signal levelser is the evaluby the quantisat both even-que the same distset. On the otower control), tation.
as follows. ents the detai
on III and seof the OFDMuantisation scV.
NTISATION Sed through aping. Oversamy (PSD) when expected, incr
OSRBB) will de7].The oversam
signal bandwquantisation ehe ΔΣ filter. 2nd order ΔΣ
ven-quantisatiare now disthe QR and
r to PWM/PPMequires the digF carrier frequ
RF. The OSRRF
ormly quantiseto 2 . The qution. The phasulse and is 0reference for
he result is thaal levels in thsation levels ss. ation of the ad
sation process uantisation antortion produc
ther hand, whthe noise prob
Section I iils of the newection IV giv
M test signal fochemes. Finall
SCHEME the processempling reducthe noise is
easing the basecrease the inmpling ratio
width and error is also
The noise tr(Fig. 2) is giv
ion [9] and thscussed. TheQ blocks an
M’ of Fig.1. gital clock (fcuency of the F is given by
ed into NP (=Ouantised phasese reference is0 degrees for
odd pulsewid
at there he ΔΣ should
djacent in the
nd odd-cts that hen the blem is
is the w odd-ve the or both ly, we
es of ces the spread seband n-band of the
(1)
is the noise
ransfer ven by:
(2)
he new e new nd the
lock) to signal
(3)
OSRRF) e, , is s taken r even dths is
(4)
Thas ampclocbantracof todd
Fig. OSR
If
pulsampone ampoddcan Phaand dimqua
Fiin thradipoinquacroscorrdashand ampmeashow
Thshow
The
Thfund
he quantised ashown in Fiplitude conditick periods. T
ndpass filteringce shows a redthree clock ped pulsewidth co
Phase referencpoint of odd num
of clock period
c
Q
EVEN
Q
ODD
3. Calculation fRRF=8.
f the quantisedsewidths, thenplitude quantis dimensionalplitudes are cod and even pu
cause a chanase Modulatiod phase quanmensional opeantiser complexig. 4 shows thhe Polar planial lines shownts of QE[
antised points sses. and responding tohed circles be
d black is for plitude quantisasured midwawn as dashed he quantised wn in Fig. 4 (b
e threshold for
he amplitudedamental spec
, with
amplitude, , g. 3. The toion for OSRRFThe output isg produces theduced amplitueriods. The phonditions is cl
Phase referencpoint of even num
of clock period
ce mber ds
ref
Tc
co Tclk
cE Tclk
for with the e
d amplitudes n the phase resation and phal operations; onfined to all tlsewidths are
nge in phase (Aon (PM) convntisation musteration and lxity.
he even-quantine. The radius w the quantised
] are illust of QO[ ]
are theo the I and Qetween each o
odd-Polar) aser ( ). The pay between twlines. phase is bas
below), given
r the quantised
e levels are ctral componeamplitudes 1,
is determined op trace showF=8 and has a ps a full squaree sinusoidal oude sinewave hase referencelearly shown.
ce mber ds
Tc
un(4Tclk,0)
un(3Tclk,0)
even-odd number
are confineference does nase quantisatio
similarly, if the odd pulsewallowed a ch
Amplitude Moversion) and st be applied.leads to a g
isation and the of the circlesd phase, . Ttrated by red] are illustrate quantised Q output of thof circles (red are the threshphase threshowo phase inc
ed on the odby
d phase is calcu
calculated bent of the thre, 0, and -1. po
by the pulsewws the maximpulsewidth of e wave, and
output. The bowith a pulsew
e for the even
RF Signal
r of clock period
ed to all the not change anon are indepenf the quantisawidths. When
hange in ampliodulation (AMso joint ampli. This is a great increas
e odd-quantisas is set by .
The even-quand dots. The ted by the bvalues of [R
he ΔΣ filters. is for even-P
hold levels forld levels, ( )crements, and
dd-Polar plane
ulated by equa
by evaluating e-level wavef
o is the pulsew
width mum f four after
ottom width n and
l
ds for
even nd so ndent ation both itude
M) to itude two-e in
ation The
ntised odd-
black R,�] The
Polar, r the ), are d are
e, as
(5) ation (6)
the form, width
cocytimPP
Figpla
SthusveFo whamfir
orresponding tycles (cE is for me delay or aPM delay in cl
g. 4. The even-qane scale for OSR
Since e spectral com
sing the Fouriersion of ourier transfor
here K is thmplitude of thrst frequency b
to the cO clockr even). pp is thadvance. pp = lock periods.
quantisation (top)RRF=8.
is a repeamponent can bier series. Her
to getrm (DFT).
he fast Fourhe fundamentabin, k=1
k cycles (cO is he pulse positi(0, … (NP-1))
) and the odd-qu
ating waveformbe generated frre, we use a ht the same res
rier transformal of the pulse
for odd) or cEion and refers) and represen
uantisation (below
m, the ampliturom one periohighly oversasult from a di
m (FFT) size
wave occurs
E clock s to the nts the
w) Polar
ude of d only
ampled iscrete
(7) e. The
in the
to thTh
two
wheA
usedreprlocadetefromwheThePW
G
Fig.
Fisignof pulsof triantwofromsym
IFi
Carat (appof th
wheeach
is the index
he odd pulsewhe amplitude t
o amplitude qu
ere the index ofter quantisatid to convertresentation toation of the ermined usingm Q block. Aere the pulse e output of Q
WM process.
Odd PWM Generation
5. Odd PWM gen
ig. 5 illustratnals using a st
quantised asewidths, PW1the line ngular wavefo
o sample increm the phase
mmetry about i
III. TEST SIGig. 6 shows thertesian ΔΣ upc
with fc=1024plicable bandwhe ΔΣ is relate
ere the index h output samp
x for the diffe
width threshold leve
uantised levels
of is selecteion, then the t the quanti
o RF using Ppulse posit
g the quantisedA change in po
edges must oQR block, d
0
P
P
Middthe odd q
7
5
3
neration.
tes the PWMtepped triangl
amplitudes: 1 and PW2, ar
and orm signal. Thements to deresponse. Th
its midpoint.
GNAL CHARAe simulation m
converters. Th4 MHz which width to WLAed to the nomi m is the num
ple of the ΔΣ, (
,
erent pulsewid
els are given bs,
,
ed in ascendin‘Polar to PWsed signals,
PWM and PPtion of the d phase, , w
osition dependsccur on the ddetermines th
0
W1
PW2
dle line of quantisation
1
3
5
M generation e wave. It sho
andre defined by t
respectively he pulsewidth couple the amhe pulsewidt
ACTERISTICmodel for test e OFDM bandequivalent to
AN). The sampinal carrier fre
mber of carrier(m=n/2, where
,
dths correspon
. by the midpoi
ng order. WM/PPM’ bloc
[ ], in PPM schemes.
PPM proceswhich is the ou
s on a change digital timing he duration of
7
9
of odd quanows two exam
. The outhe crossing p
and the stepmust change
mplitude resph then main
CS OF OFDMsignal OFDMdwidth (B) waa Bofdm of 16 M
pling frequencyequency fc. r periods betwe n is an intege
(8)
nding
nt of
(9)
ck is Polar
The ss is utput of grid. f the
ntised mples utput oints pped with
ponse ntains
M into as set MHz y (fs)
(10) ween er).
Figoff WevraIf ofnoinbesu
AOSto upnofachhanofroar
g. 6. OFDM as infset carrier.
When n=1 and very half perioate. In this wo
is the bin f subcarriers, ominal numbecluding the
etween adjaceummarized in T
Para
Modulat
Frequenc
OS
Oversampling
Offset f
IA spectrum pSRRF of 16 an urms= 1) ob
pconverter is sominal positiocilitate the un
hannel 1. The armonic is situoise is lowest om fc and maxround that regi
nput the I and Q s
m=1/2, the puod of the carrork we use m=frequency spatherefore Bof
er of subcarrnull sub-car
ent channels. Table I.
TSIMULATIO
ameter
ted Signal
y carrier, fc
SRBB
g ratio (OSRRF)
N
A
f
frequency
IV. SIMULATplot of a pulsnd an input sigbtained at thshown in Fig. on of the carnderstanding o image is preuated in chann
in channel 0ximum attenuaion (ΔΣ-filters
signal to Cartesian
ulse width andrier, which is
=1 (n=2) and uacing betweenfdm is equal toriers in the crriers forming
The simulat
TABLE I ON PARAMETERS
Q
20 MHz,
TION RESULse waveform gnal level, u= he output of
7. The adjacerrier are drawf the plot. The
esent in channnel 3 with the
0 as the NTF ation of quants with MOD2)
n ΔΣ upconverter
d position is ups the highest uupdate every pn the active tono . Nchannel bandg the guard tion paramete
Value
PSK, OFDM
1024 MHz
64
16
20
16
1 MHz
guard band 0.2
TS with an RF -7 dB (with rthe Cartesia
ent channels awn on the fige signal is presnel -1 and thee highest noisof the ΔΣ op
tisation noise o).
rs for an
pdated update period. nes (A) is the
dwidth, band
ers are
5Bofdm
carrier respect an ΔΣ and the gure to sent in e third e. The perates occurs
Fig. ΔΣ u
Thoddadjashifspecpowweras w
Fig. (ACP
Fi
the Caris ththe to esignthe thanquaeven
-7
-6
-5
-4
-3
-2
-1
Spec
trum
relat
ive
to th
e O
FDM
sign
al (d
B)
-7
-6
-5
-4
-3
-2
-1
AC
P no
rmal
ised
to si
gnal
pow
er (d
B)
7. Spectrum plot upconverter with o
he out-of-band-quantisation acent channelfted one chanctral images.
wer in the adjre calculated. well as distorti
8, Cartesian ΔΣP in adjacent chan
ig. 8 shows a psix adjacen
rtesian ΔΣ schhe optimum infigure, the od
even-quantisatnal levels is thodd-quantisat
n the even-quantisation schen-quantisation
95070
60
50
40
30
20
10
0
Ch -3
-40 -3570
60
50
40
30
20
0
0
even
odd
of even-quantisatoffset OFDM sign
nd distortions schemes are
l powers (ACnnel to the rThe ACPs w
jacent channeThe noise pow
ion arising fro
Σ with even-quannnel vs. input lev
plot of input lnt channels oheme. The shanput signal levdd-quantisatiotion for most ihe improvemtion scheme huantisation sceme has at lean scheme. Ag
1000Freque
P
c
Ch -2 Ch -1
-30 -25Input Pow
tion and odd-quannal.
for both evencompared by
CPs). The deright to examwhich are defel divided by wer includes m PPM.
ntisation and odel).
level (dB) agaobtained afte
ape of the curvvel for best SN
on has reducedinput signal leent less obviohas at least 4
cheme. In chaast 5.57 dB lgain, it can
1050ency (MHz)
Positionof
carrier
Ch 0 Ch 1
-20 -15wer-to-noise (dB)
ntisation in Cartes
n-quantisationy calculating esired signal
mine the resufined as the n
the signal poquantisation n
d-quantisation sc
ainst ACP (dBer simulating ves indicates -NR. As showd ACP compevels; only at lous. In chann4.83 dB less Aannel 0, the less ACP thanbe observed
EveOdd
Ch 2 Ch 3
-10 -5
Channel 2 (even)Channel 3 (even)Channel 0 (even)Channel -1 (even)Channel -2 (even)Channel -3 (even)Channel 2 (odd) Channel 3 (odd)Channel 0 (odd)Channel -1 (odd)Channel -2 (odd)Channel -3 (odd)
sian
n and their was
ultant noise ower noise
cheme
B) for the
-7dB wn in pared large
nel 2, ACP odd-
n the that
1100
end
0
channel 3 (Fig.7) which represents the third harmonic has the highest noise. Channel -1 representing the image has the second highest noise. Channel 0 has lower noise than channel 2 as channel 0 is centered at fc. This plot further validates the conclusions drawn from Fig. 7.
V. CONCLUSION
This paper compares even-quantisation and odd-quantisation schemes for Cartesian ΔΣ upconverters. OFDM is used as the input signal. The characteristics of the input test signals and the OSR for both schemes are kept the same. The overall performance of the even-quantisation scheme is worse than the odd-quantisation scheme as the even-quantisation structure has an inherently higher noise floor. It can be observed that the third harmonic is the biggest noise contributor followed by the image. Interestingly, the overall better performances of the odd-quantisation scheme occur at lower input signal levels. These levels benefit from the lower first quantisation step of the odd-quantisation scheme. The benefit is lost when the input signal level rises to within about 7dB of the optimum signal level. The image and third order distortions dominate the performance at large signal levels and make signal tuning by using frequency offsetting at baseband a non-attractive proposition. The type of quantisation does not improve this aspect of the output spectrum. Tuning by changing the sample rate would obviate the need for offsetting and so avoid the problem.
VI. REFERENCES
[1]
[2]
[3]
[4]
[5]
[6]
[7]
[8]
[9]
[10]
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