[IEEE 2011 NORCHIP - Lund, Sweden (2011.11.14-2011.11.15)] 2011 NORCHIP - An empirical study of the...
Transcript of [IEEE 2011 NORCHIP - Lund, Sweden (2011.11.14-2011.11.15)] 2011 NORCHIP - An empirical study of the...
An empirical study of the stability of 4th-order Incremental-I:�-ADCs
Johannes Uhlig and Rene Schliffny
Department of Electrical Engineering
Technische Universitat Dresden, Germany
Emails:{uhlig.schueffn}@iee.ettu-dresden.de
Abstract-In order to find relationships between NoiseTransfer-Function (NTF) characteristics and stability of a Incremental-Delta-Sigma ADC (I-DS-ADC) 40.000 different NTF has been investigated. A fast and easy to use criterion to determine, if an NTF of an I-DS-ADC of 4th-order is likely to be stable was found. The novel criterion is fast and easy to use and covers a much bigger variety of possible NTFs compared to recent criteria.
Index Terms--delta sigma, stability
I. INTRODUCTION
Incremental Delta-Sigma ADCs (I-DS-ADCs) are Delta
Sigma data converter whose memory elements are initially
reset before each new conversion. The input signal is assumed
to be stable during each conversion. I-DS-ADC show many
advantages for DC-Signal conversion such as lower offset
and gain errors, multiplex capabilities and much easier digital
filtering [l]. The analysis of the stability of a DS-ADC with an order
higher than 2 in general and of I-DS-ADCs in particular is
still an open issue when designing such ADCs.
Higher order DS-ADC consists of cascaded integrators with
various feedback or feed forward paths. Stability of a DS-ADC
means, that all output values of these integrators are limited
during each conversion for the whole dedicated input signal
range. Up to now, there is no successful analytical approach
to determine the stability of DS-ADCs with order higher than
2 [2]. The behavior of an DS-ADCs is uniquely defined by
its Noise-Transfer-Function (NTF) and its Signal-Transfer
Function (STF) (see Fig. 1). The NTF is the transfer function
from the quantization noise input of the linearized quantizer
to the modulators output and the STF the one from the input
to the output of the modulator. Typically the STF is chosen to
be one. In this case the NTF determines the behavior of the
DS-ADCs and thereby its stability.
Available approaches to check an NTF for stability are either
to complex, require significant computing power or give very
conservative results.
Steiner and Young [3] presented a framework for analyzing
the stability by using a state-space transformation which
Manuscript received October 7, 20 II. This research is founded by the European Union (European Regional
Development Fund) and the State of Saxony
978-1-4577-0516-8/11/$26.00 ©2011 IEEE
Loop- V,",o"o
Filter
Fig. I. General block diagram of a DS-ADC. The behavior is completely defined by its Noise-Transfer-Function (NTF) and Signal-Transfer-Function (STF)
converts the modulator loop in a way that all state-space
variables are decoupled. Wong [4] combined this approach
with continuous-time embedding and Poincare map analysis.
However his simulation results seem not to confirm the theory
and the mathematics beyond the continuous-time embedding
rely more or less on graphical analysis or are nearly in
tractable.
An comprehensive summary of recent approaches can be
found in [2]. It turns out that even if a pure analytical solution
to verify the NTFs stability will be found the mathematics will
be rather complex because of the strong non-linearity of the
internal quantizer.
Other approaches combine analytical analysis with simula
tion or computation. Schreier [5] presented an algorithm for
computing an convex positively invariant set which contains
all possible states of the modulators integrators. However
the computational effort is pretty high especially for higher
order modulators. Ritoniemi [6] uses root-locus analysis to
investigate the stability but needs simulations to determine
the actual quantizer gain for each cycle. Yang [7] presents
a method for designing stable NTFs also based on root-locus
analysis but his results are very conservative and therefor not
applicable for the design of high resolution NTFs.
When designing an NTF with optimized characteristics like
resolution, signal swing or easy feasible coefficients an fast
and easy method to check if an NTF is very likely to be stable
is essential because a large number of different NTFs has to
be investigated in this design step. All previously described
approaches are either to complex and therefor not automatable
or require high computational resources. Currently, the most
used criterion is the modified Lee criterion [8] which is based
Fig. 2. Root-Locus for an NTF of 4th-order for varying quantizer gains A
on the criterion published in [9]. This criterion says that an NTF is likely to be stable if the maximum magnitude
found with
NTFquantIn =
Vq'i�tIn = NTF - 1 (6)
and its Infinity-Norm IINTFquantInlloo and Root-MeanSquare Gain rms NT F _qi can be derived.
III. POOL OF CHECKED NTFs
In order to analyze relationships between certain NTF characteristics and the stability 40.000 NTFs of 4th-order has been investigated. All NTFs are in the form
NTF (z) =
(z - 1)4 (7)
(z - pd (z - P2) (Z - P3) (Z - P4)
IINTFlloo = max (INTF (ejw)l) < 1.5 wE [O,IT]
(1) and their poles Pn where randomly chosen with the restriction that
of the NTF, also known as the infinity norm , is smaller than 1.5. Beside the fact that this criterion is not sufficient a lot of freedom of design will get lost when this criterion is used as we will show in the next paragraph.
Based on an empirical study using 40.000 random NTFs we will formulate a new criterion which is fast and easy to use but cover a much bigger variety of NTFs.
II. CHARACTERISTICS OF THE N OISE TRA NSFER FUNCTION
As stated before the behavior of an DS-ADC and therefor its stability is solely defined by its NTF. Goal of our research is to find relationships between certain NTF characteristics and the stability of the NTF.
Important characteristics of an NTF are the Infinity-Norm
which is the maximum magnitude of the NTF according to Eq. 1, and the Root-Mean-Square Gain which is
IT
rmS-f}ainNTF = � J INTF (ejw)12 dw (2)
o
The NTF describes the transfer function of the quantization noise under the assumption that the gain of the linearized quantizer is 1. Actually the gain of the quantizer is
A =
sign (VquantIn) . Vref VquantIn
which leads to a modified NTF depending quantizer gain with [8]
NTF NTF,\ =
A + (1- A)NTF
(3)
on the actual
(4)
If A decreases the poles move towards the unit circle (see Fig. 2). If A < Amin there are poles which lies out of the unit cycle and the modulator tends to get unstable [10]. From Amin a maximum input voltage of the quantizer
1 QuantInmax_stable = � (5)
/\mzn can be calculated for which all poles remain in the unit circle if this voltage is not exceeded.
Like the NTF, a transfer function from the quantization noise input to the input of the quantizer (see Fig. 1) can be
• there are two conjugate complex pairs or one conjugate complex pair and two real poles
• the real part of each pole is Re (Pn) > 0 • the absolute value of each pole is I Pn I < 1. Each NTF has been checked for stability under the as
sumption that the normalized input voltage range is ±0.5Vref and the I-DS-ADC operates for 1000 cycles for each input value. Stability of an I-DS-ADC can more easily be checked by simulation than for conventional DS-ADC because the input is assumed to be stable and the modulator will operate for a certain number of cycles only. Each NTF has been simulated with 220 linear distributed input values in the range [0 -+ 0.5Vrefl and in addition with 230 linear distributed input values in the range [0.4Vref -+ 0.5Vrefl because instability is more likely if the input voltage increases. An NTF is considered to be stable if the maximum observed quantizer input voltage is max (!VquantInl) < QuantInmax_stable. However, also a much larger bound for max (IVquantInl) e.g. 1000 could be chosen because our investigations show that there is a certain input value for which the quantizers input value starts to oscillate and rises towards infinity provided
�4 "
:0 3 .8 .,
I H OJ
� 2 ,:: ....... ....., ,:: tj ;:l 1
0' 1
Lee crit {jon
-'" " ' .
. •
•
2 3 4
infinity norm NT F
stable
unstable
•
5 6
Fig. 3. Maximum quantizer input voltage {lQuantInmax_stable {Ill Amin for which all Poles of the NTF are within the unit circle ploted
vs. the infinity norm IINTFlloo' Green NTFs are stable while red NTFs are unstable. The blue line shows the border for potential stable NTF specified by the modified Lee criterion which would classify 11% of the stable NTFs as stable
� 4 • •
stable •
• • • •
• • • unstable '"
::c 3 .8 '"
I H d � 2
� ....... ....., � (j ;:l I
0' 0.5 I 1.5 2 2.5 3 3.5 M
rmsGain NT Fquantln
Fig. 4. Maximum quantizer input voltage vQuantInmax_stable Vl/ Amin for which all Poles of the NTF are within the unit circle ploted
vs. rms NT F _qi for all random NTFs which are flat and therefor does not have poles in their magnitude vs. frequency. The boundary can be described
with VI/Amin = 1.06· rmSNTF_qi + 0.08 and Rpos = 80%
� 4 • stable
• • unstable • <u 3 :8 H d � 2 �
....... ....., � (j ;:l I
0' 0.5 I 1.5 2 2.5 3 3.5 4
rmsGain NT Fq'uantI n
Fig. 5. Like Fig. 4 but both flat NTFs and NTFs with poles are used. The Ratio Rpos drops to Rpos = 45%. The boundry can be described with
VI/Amin = 3.4· rmSNTF_qi - 2.26
� 4
'" 3 :8 H d �
� 2 ....... ....., � (j ;:l
0'
infinity norm NT FquantIn
Fig. 6. Maximum quantizer input voltage vQuantInmax_stable VI/Amin plotted vs. IINTFquantlnlloo' The boundary can be described
with VI/ Amin = 1.16· liNT Fquantln 1100 - 0.38
that max(!VquantInl) > QuantInmax_stable occur in a certain
conversion step.
IV. NTF CHARACTERISTICS VS. STABILITY
The quality of a criterion to select potential stable NTFs
can be measured as the ration
#positive classified NTFs Rpos = (8)
#all stable NTFs
between the number of NTFs which will be classified as stable
and the total number of stable NTFs.
If we apply the former described modified Lee criterion
on the pool of NTFs to select potential stable NTFs, only
Rpos = 11 % of the stable NTFs will be selected (see Fig.
3). However we did not find any NTF with II NT FII 00 < 1.5 which is unstable under the condition named in Sec. III. This
confirms the modified Lee criterion but a lot of freedom of
design will get lost because only a small part of the stable
NTFs will be classified as potential stable.
Under the assumption of white quantization noise the
transfered noise to the quantizer input should depend on
rms NT F _qi . Because instability is very likely if the quan
tizer input voltage exceeds QuantI nmax_stable stability of
an NTF should depend on the ratio between rms NT F _qi and
QuantI nmax_stable. Even though the quantization noise is not white for DC
Inputs, we found a distinct relationship between rms NT F _qi and QuantInmax_stable. If only flat NTFs (see Fig. 8) are
considered a ratio of Rpos = 80% can be achieved by
using a linear relationship between {/ QuantI nmax_stable and
rmSNTLqi (see Fig. 4). If also NTFs with poles will be taken
into account this ratio drops to Rpos = 45% (see Fig. 5).
Apparently modulators tend to be unstable even for mod
erate values of rmSNTF_qi if whose NTF is not flat. We
could identify the liNT FquantIn 1100 to be significant be
side rms NT F _qi for the stability. Fig. 8 shows one sta
ble and one unstable NTF with nearly identical character
istics beside a significant difference for the infinity norm
IINTFquantInlloo' The significance of rmSNTF_qi together
with the IINTFquantlnlloo for the stability is also obvious in
Fig. 7.
The boundary between stable and unstable NTFs can be
described with
canst = (rmsNTF_qi - rmSNTF_qi,max( {/l/Amin))' . (1lNTFquantInlloo -IINTFquantInlloo,max ({/l/Amin))
(9)
with rmSNTF qi max and IINTFquantInl1 based on the - , oo,max boundaries shown in Fig. 5 and Fig. 6
rms NT F _qi, max
liNT FquantInlloo,max
�+2.26 3.4
�+O.38 l.16
(10)
(11)
; �> 1.1 < 1.1 � �> 1.2 < 1.2 � �> 1.4 < 1.5
• � � " 6 " 6 .. " 6 , " ,
"," 0-
0. "," f-< 4 f-< 4 f-< 4 <: .. <: <: � � � : i �
2 � 2 �
2 0 0 0 . .. , . � � � I I I ....,
0.5 1 1.5 2 2.5 ....,
0.5 1 1.5 2 2.5 ....,
0.5 1 1.5 2 2.5 .� � .� rms _gainNTFquan-tfn rms _gainNTFwuan-tIn rms _gain NTFquan-tIn
" " � o/i7;\ > 1.6 < 1.6 �> 1.8 < 1.9 � 2.1 < 2.2
• � " " 6 " 6 ........... , "
"," 0-
" f-< 4 f-< 4 <: <: � � � 2 ·� tI �S � � �··
� 2 0 0 -; ...... ;. '
� � ... .. .
I I ....,
0.5 1 1.5 2 2.5 ....,
0.5 .� .�
.... ,
1.5
.
.. . · ,1 .:
2 2.5
" 6 " "," f-< 4 <: � � 2 0
� I ...., .�
.. , .. . . . '
...... ·.:.I. s-
. :.;,;,-
';p.'
0.5 1 1.5 2 2.5
rms _gainNTFquan-tfn rms _gain NT F quan-tI n rms _gainNTFquan-tfn
Fig. 7. IINTFquantlnl1 vs. rmSNTF_qi for different intervals of {.Ii7\, blue line shows boundary between areas treated as stable or unstable according to Eq. 12 with canst = 0':04
rti' o
:"'.. �50 � h �100
Frequency .:��
Frequency :��
Fig. 8. Magnitude of two exemplary NTF to illustrate the difference between NTFs which are flat and NTFs which has poles in their magnitude. The green NTF is stable, the red NTF unstable. Both NTFs show nearly identical characteristics with rmS--9ainNTF = 1.6, rmSNTF_qi = 1.3, liNT FII= = 2.0 and QuantInmax_stable = 3.9 resp 4.0 but differ significantly with IINTFquantInll= = 1.6 resp. 2.1.
According to Eq. 9 - 11 an NTF is likely to be stable if
{h/Amin + 2.26 rmSNTF_qi <
3.4 or
canst IINTFquantInlloo <
�+2.26 + (12)
rmSNTF_qi - 3.4
{h/Amin + 0.38
+ 1.16
If canst = 0.04 is choosen there is no unstable NTF in the
investigated pool which will misleadingly classified as stable.
With this criterion (see also Fig. 7) a ratio Rpos = 85% can be
reached which is a considerable improvement compared to the
11 % which can be reached with the Lee criterion. Increasing
canst will improve Rpos further but at the cost that it will
be more likely to get unstable NTFs which are misleadingly
classified as stable.
V. CONCLUSION
A novel criterion for selecting stable NTFs for 4th-order
I-DS-ADCs has been presented. The criterion is is fast and
easy to use and increases the variety of NTFs which can be
considered significantly compared to the so far used Lee crite
rion. Further research will be done to generalize the criterion
to cover also NTFs of different order and to consider arbitrary
input signal ranges. The criterion was found empirical. Work
will be done to investigate the analytical background of the
found criterion.
REFERENCES
[1] J. Markus and G. C. Ternes. Design theory for high-order incremental converters. Budapest University of Technology and Economics , Dept. of Measurement and Information Systems. [Online]. Available: www.mit.bme.hu/ markus/pubs/wisp2003_pres.pdf
[2] J. Reiss, "Understanding Sigma-Delta Modulation: The Solved and Unsolved Issues;' Journal of the Audio Engineering Society, vol. 56, no. 1-2, pp. 49-64, 2008.
[3] p. Steiner and W Yang, "A framework for analysis of high-order sigmadelta modulators," IEEE Trans. Circuits Syst. II, vol. 44, no. 1, pp. 1-10, 1997.
[4] N. Wong and T-S. Ng, "Dc stability analysis of high-order, lowpass modulators with distinct unit circle ntf zeros," IEEE Transactions on
Circuits and Systems II: Analog and Digital Signal Processing, vol. 50, no. 1, pp. 12-30, 1 2003.
[5] R. Schreier, M. Goodson, and B. Zhang, "An algorithm for computing convex positively invariant sets for delta-sigma modulators," Circuits and Systems I: Fundamental Theory and Applications, IEEE Transactions on, vol. 44, no. 1, pp. 38 -44, jan 1997.
[6] T Ritoniemi, T Karema, and H. Tenhunen, "Design of stable high order I-bit sigma-delta modulators," in Circuits and Systems, 1990., IEEE
International Symposium on, may 1990, pp. 3267 -3270 volA [7] C.-c. Yang, K.-D. Chen, W-C. Wang, and T-H. Kuo, "Transfer function
design of stable high-order sigma-delta modulators with root locus inside unit circle," in ASIC, 2002. Proceedings. 2002 IEEE Asia-Pacific
Conference on, 2002, pp. 5 - 8. [8] R. Schreier and G. C. Ternes, Understanding Delta-Sigma Data Con
verters, S. V. Kartalopoulos, Ed. IEEE Press, John Wiley & Sons, INC, 2005.
[9] W L. Lee, "A novel higher-order interpolative modulator topology for high resolution oversampling aid converters," Master's thesis, Massachusetts Institute of Technology, Cambridge, 1987.
[10] Y. Wang, K. Muhammad, and K. Roy, "Design of sigma–delta modulators with arbitrary transfer functions," IEEE Trans. Signal Pro
cess., vol. 55, no. 2, pp. 677-683, 2007.