April 14, 2014 ECEN 5341,2013 Electroporation and Electric Shock
Second Order RLC Filters - Electrical, Computer & Energy...
Transcript of Second Order RLC Filters - Electrical, Computer & Energy...
ECEN 2260 Circuits/Electronics 2 Spring 20072-10-07 P. Mathys
Second Order RLC Filters
1 RLC Lowpass Filter
A passive RLC lowpass filter (LPF) circuit is shown in the following schematic.
◦
◦ ◦
◦
•
•
R L
C
−
vS(t)
+
−
vO(t)
+
Using phasor analysis, vO(t)⇔ VO is computed as
VO =
1jωC
R + jωL + 1jωC
VS =1
LC
(jω)2 + jω RL
+ 1LC
VS .
Setting ω0 = 1/√
LC and 2ζω0 = R/L, where ω0 is the (undamped) natural frequency andζ is the damping ratio, yields
VO =ω2
0
(jω)2 + jω 2ζω0 + ω20
VS ⇐⇒ v(2)O (t) + 2ζω0 v
(1)O (t) + ω2
0 vO(t) = ω20 vS(t) .
The blockdiagram that represents this differential equation is
ω20 +
∫ ∫ •
ω20
•
2ζω0
+
+
−
++
vS(t) v(2)O (t) v
(1)O (t) vO(t)
Unit Step Response. By definition, the unit step response g(t) of a circuit is the zero-stateresponse (ZSR) to the input vS(t) = u(t). For the 2’nd order LPF considered here the unitstep response is of the form (if ζ 6= 1)
g(t) = K1 es1t + K2 es2t + 1 , t ≥ 0 =⇒ g(1)(t) = s1K1 es1t + s2K2 es2t , t ≥ 0 ,
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with initial conditions g(0) = 0 and g(1)(0) = 0. The values of s1 and s2 are the solutions ofthe characteristic equation
s2 + 2ζω0s + ω20 = 0 =⇒ s1,2 =
(− ζ ±
√ζ2 − 1
)ω0 ,
and the properties of g(t) change fundamentally depending on whether ζ > 1, ζ = 1, orζ < 1.
Overdamped Case, ζ > 1. In this case the characteristic equation has two real solutions
s1 = −α1 , α1 = (ζ −√
ζ2 − 1) ω0 , and s2 = −α2 , α2 = (ζ +√
ζ2 − 1) ω0 .
Note that α1 < α2. The unit step response is of the form
g(t) = K1 e−α1t +K2 e−α2t +1 , t ≥ 0 =⇒ g(1)(t) = −α1K1 e−α1t−α2K2 e−α2t , t ≥ 0 .
Using initial conditions g(0) = 0 and g(1)(0) = 0 yields
K1 + K2 = −1 ,
α1K1 + α2K2 = 0 .=⇒
[1 1
α1 α2
] [K1
K2
]=
[−1
0
].
From this K1 and K2 are obtained as
K1 =−α2
α2 − α1
, K2 =α1
α2 − α1
,
and thus the unit step response for a 2’nd order overdamped LPF is
g(t) = 1− α2 e−α1t − α1 e−α2t
α2 − α1
, t ≥ 0 .
Note thatg(1)(t) =
α1 α2
α2 − α1
(e−α1t − e−α2t) , t ≥ 0 ,
and therefore g(1)(t) = 0 requires that e−α1t = e−α2t which can only happen at t = 0 ort =∞ if α1 6= α2. This implies that the extrema of g(t) occur at t = 0 (where g(0) = 0) andat t =∞ (where g(∞) = 1) and thus g(t) has no overshoot.
Critically Damped Case, ζ = 1. In this case the characteristic equation has one realdouble solution
s1 = s2 = −α , α = ω0 ,
and the unit step response is of the form
g(t) = K1 e−αt + K2 t e−αt + 1 , t ≥ 0 ,
=⇒ g(1)(t) = −αK1 e−αt + K2 e−αt − αK2 t e−αt , t ≥ 0 .
Using initial conditions g(0) = 0 and g(1)(0) = 0 yields
K1 = −1 , K2 = −α ,
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and thus the unit step response for a 2’nd order critically damped LPF is
g(t) = 1− (1 + αt) e−αt , t ≥ 0 .
Note thatg(1)(t) = α2t e−αt , t ≥ 0 ,
and therefore g(1)(t) = 0 requires either t = 0 or t = ∞, which implies that the extrema ofg(t) are 0 (at t = 0) and 1 (at t =∞) and thus g(t) has no overshoot.
Underdamped Case, ζ < 1. In this case the characteristic equation has two complexsolutions which are conjugates of each other
s1 = −α + jβ , and s2 = s∗1 = −α− jβ , where α = ζω0 , β =√
1− ζ2 ω0 .
The unit step response is of the form
g(t) = K1 es1t + K2 es2t + 1 , t ≥ 0 =⇒ g(1)(t) = s1K1 es1t + s2K2 es2t , t ≥ 0 .
Substituting s1,2 = −α± jβ and using initial conditions g(0) = 0 and g(1)(0) = 0 yields
K1 + K2 = −1 ,
(−α+jβ)K1 − (α+jβ)K2 = 0 .=⇒
[1 1
−α+jβ −α−jβ
] [K1
K2
]=
[−1
0
].
From this K1 and K2 = K∗1 are obtained as
K1 =−β + jα
2β= ρ ejφ , K2 =
−β − jα
2β= ρ e−jφ ,
where
ρ =
√α2 + β2
2β=
1
2√
1− ζ2, and φ = π − tan−1 α
β= π − tan−1 ζ√
1− ζ2.
Thus, the unit step response for a 2’nd order underdamped LPF is
g(t) = 1 + ρ e−αt(ej(βt+φ) + e−j(βt+φ)
)= 1 + 2ρ e−αt cos(βt + φ) , t ≥ 0 ,
or, with ρ and φ substituted
g(t) = 1− e−αt√1− ζ2
cos(βt− tan−1 ζ√
1− ζ2
), t ≥ 0 .
To obtain a formula for g(1)(t) easily, first note that s2K2 = (s1K1)∗ and
s1 K1 = (−α + jβ)−β + jα
2β=
α2 + β2
2jβ.
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Then use g(1)(t) =(s1K1 ejβt + s2K2 e−jβt
)e−αt to obtain
g(1)(t) =α2 + β2
βe−αt
(ejβt − e−jβt
2j
)=
α2 + β2
βe−αt sin βt , t ≥ 0 .
To find the times where the extrema of g(t) occur, set g(1)(t) = 0 and solve for t. The sinehas zero crossings for βt = kπ and, for k = 0, g(t) = g(0) = 0 clearly has a minimum.The largest and most interesting maximum (due to underdamping) of g(t) happens whenbt = π ⇒ t = π/β. The value of the maximum is computed as
gmax = g(π
β
)= 1 + 2ρ e−πα/β cos(π + φ) = 1 +
e−πζ/√
1−ζ2√1− ζ2
cos(tan−1 ζ√
1− ζ2
).
Using the identity
cos(tan−1 x√
1− x2
)=√
1− x2 ,
the final result is
gmax = 1 + e−πζ/√
1−ζ2=⇒ Overshoot in %: 100 e−πζ/
√1−ζ2
.
The following graph shows the unit step response g(t) for several values of ζ.
0 0.5 1 1.5 2 2.5 3 3.5 4 4.5 50
0.2
0.4
0.6
0.8
1
1.2
1.4
1.6
t in msec
g(t)
Unit Step Responses of Second Order LPF, ω0=3141.5927
ζ=0.2ζ=0.5ζ=0.70711ζ=1ζ=2
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Frequency Response. From the phasor analysis the system function of the LPF is obtainedas
H =VO
VS
=ω2
0
ω20 − ω2 + j 2ζω0 ω
.
The magnitude and the phase of H are
|H| = ω20√
(ω20 − ω2)2 + (2ζω0 ω)2
, and ∠H = − tan−1 2ζω0 ω
ω20 − ω2
.
Note that, at ω = ω0,
|H|ω0 =1
2ζ, and ∠Hω0 = −90◦ ,
and thus ζ and ω0 can be easily determined from the magnitude and phase of H.
2 RLC Bandpass Filter
A passive RLC bandpass filter (BPF) circuit is shown in the following schematic.
◦
◦ ◦
◦
•
•
•
•
R
L C
−
vS(t)
+
−
vO(t)
+
Using phasor analysis, vO(t)⇔ VO is computed as
VO =
jωL(jω)2LC+1
R + jωL(jω)2LC+1
VS =jω 1
RC
(jω)2 + jω 1RC
+ 1LC
VS .
Setting ω0 = 1/√
LC and 2ζω0 = 1/(RC) yields
VO =jω 2ζω0
(jω)2 + jω 2ζω0 + ω20
VS ⇐⇒ v(2)O (t)+2ζω0 v
(1)O (t)+ω2
0 vO(t) = 2ζω0 v(1)S (t) .
The blockdiagram that represents this differential equation is (after integrating both sides
so that the input is vS(t) rather than v(1)S (t))
2ζω0 +∫ ∫
ω20
•
2ζω0
+
+
−
++
∫vO(τ)dτvS(t) v
(1)O (t) vO(t)
vO(t)
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Frequency Response. From the phasor analysis the system function of the BPF is obtainedas
H =VO
VS
=j 2ζω0ω
ω20 − ω2 + j 2ζω0ω
.
The magnitude and the phase of H are
|H| = 2ζω0 ω√(ω2
0 − ω2)2 + (2ζω0 ω)2, and ∠H = π/2− tan−1 2ζω0 ω
ω20 − ω2
.
Note that, at ω = ω0 (the center frequency of the BPF),
|H|ω0 = 1 , and ∠Hω0 = 0◦ .
To obtain the lower half-power (or -3dB) frequency ω3− of the BPF, set
ω20 − ω2
3− = 2ζω0ω3− =⇒ ω3− =(√
1 + ζ2 − ζ)ω0 .
Similarly, the upper half-power (or -3dB) frequency ω3+ of the BPF is obtained from
ω23+ − ω2
0 = 2ζω0ω3+ =⇒ ω3+ =(√
1 + ζ2 + ζ)ω0 .
Thus, the half-power (or -3dB) bandwidth of the BPF is equal to 2ζω0, and ζ and ω0 cantherefore be determined from the magnitude and phase of H.
c©2003–2007, P. Mathys. Last revised: 2-12-07, PM.
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