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I. Introduction to Wave Propagation - NYU Tandon...
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Transcript of I. Introduction to Wave Propagation - NYU Tandon...
July, 2003 © 2003 by H.L. Bertoni 1
I. Introduction to WavePropagation
• Waves on transmission lines• Plane waves in one dimension• Reflection and transmission at junctions• Spatial variations for harmonic time
dependence• Impedance transformations in space• Effect of material conductivity
July, 2003 © 2003 by H.L. Bertoni 2
Waves on Transmission Lines
• Equivalent circuits using distributed C and L
• Characteristic wave solutions
• Power flow
July, 2003 © 2003 by H.L. Bertoni 3
Examples of Transmission Lines
I(z,t) +
V(z,t) - z
I(z,t) +
V(z,t) -
Dielectric
Conductors
Strip Line
Coaxial Line
Two-Wire Line(Twisted Pair)
July, 2003 © 2003 by H.L. Bertoni 4
Properties of Transmission Lines (TL’s)
• Two wires having a uniform cross-section in one(z) dimension
• Electrical quantities consist of voltage V(z,t) andcurrent I(z,t) that are functions of distance z alongthe line and time t
• Lines are characterized by distributed capacitanceC and inductance L between the wires– C and L depend on the shape and size of the conductors
and the material between them
July, 2003 © 2003 by H.L. Bertoni 5
Capacitance of a Small Length of Line
The two wires act as a capacitor. Voltage applied to the wires
induces a charge on the wires, whose time derivative is the current.
Since the total charge, and hence the current, is proportional to
the length of the wires. Let the constant of proportionality be
Farads/meter. Then
l
C
I t CldV t
dt( )
( )=
I(t) +
V(t) -
l
Open circuitE
July, 2003 © 2003 by H.L. Bertoni 6
Inductance of a Small Length of Line
The wire acts as a one - turn coil. Current applied to the wires induces
a magnetic field throught the loop, whose time derivative generates the
voltage. The amount of magnetic flux (magnetic field area), and hence
the voltage, is proportional to the length of the wires. Let the constant
of proportality be Henrys/meter. Then
×
=
l
L
V t LldI t
dt( )
( )
I(t) +
V(t) -
l
Short circuitB
July, 2003 © 2003 by H.L. Bertoni 7
C and L for an Air Filled Coaxial Line
a
b
Permittivity of vacuum: Farads/m
Permeability of vacuum: Henrys/m
Cb a
L b ao o
o
o
=( )
= ( )
≈
≡ ×
−
−
22
10364 10
9
7
πε µπ
επ
µ π
lnln
Suppose that mm and mm. Then
pF/m and H/m
Note that
m/s and
a b
C L
LC
L
C
b a
o o
o o
o
o
= =
= = = =
= = × =( )
= =
0 5 2
24
40 14
20 277
1 13 10
24
2377 83 28
.
ln.
ln.
ln ln.
πε µπ
µ
µ ε πµε π
Ω
July, 2003 © 2003 by H.L. Bertoni 8
C and L for Parallel Plate Line
w
h
z
Note that for air between the plates and so that
m/s
Cw
hL
h
w
LC
L
C
h
w
h
w
o o
o o
o
o
= =
= =
= = × = =
ε µ
ε ε µ µ
µ εµε
1 13 10 3778 Ω
July, 2003 © 2003 by H.L. Bertoni 9
Two-Port Equivalent Circuit of Length ∆z
I(z,t) +
V(z,t)
-z z+∆z z
L∆z C ∆z
I(z,t) +
V(z,t)
-
+ I(z +∆z,t)
V(z+∆z,t)
-Kirchhoff circuit equations
or
V z t L zI z t
tV z z t I z t C z
V z z t
tI z z t
V z z t V z t
zL
I z t
t
I z z t I z t
z
( , )( , )
( , ) ( , )( , )
( , )
( , ) ( , ) ( , ) ( , ) ( , )
= + + =+
+ +
+ −= −
+ −= −
∆ ∆ ∆∆
∆
∆∆
∆∆
∂∂
∂∂
∂∂
CCV z z t
t
∂∂
( , )+ ∆
July, 2003 © 2003 by H.L. Bertoni 10
Transmission Line Equations
Taking the limit as gives the Transmission Line Equations
These are coupled, first order, partial differential equations whose solutions
are in terms of functions ( - / ) and that are determined by
the sources. The solutions for voltage and current are of the form
( - / ) +
∆z
V z t
zL
I z t
t
I z t
zC
V z t
t
F t z v G t z v
V z t F t z v G t z v I
→
= − = −
+
= +
0
∂∂
∂∂
∂∂
∂∂
( , ) ( , ) ( , ) ( , )
( / )
( , ) ( / ) (zz tZ
F t z v G t z v
vF t z v G t z v L
ZF t z v G t z v
vZF t z v G t z v C F
, ) ( / )
' '( / ) ' '( / )
' '( / ) '
= +[ ]
− +[ ] = − +[ ]
− +[ ] = −
1
1 1
1
( - / ) -
Direct substitution into the TL Equations, and using the chain rule gives
( - / ) - ( - / ) -
( - / ) + (tt z v G t z v
F G
- / ) +
where the prime (' ) indicates differentiation with respect to the total variable
inside the parentheses of or .
'( / )+[ ]
July, 2003 © 2003 by H.L. Bertoni 11
Conditions for Existence of TL Solution
For the two equations to be satisfied
and
Multiplying both sides of the two equations gives or
m/s
Dividing both sides of the two equations gives or
and are interpreted as the wave velocity and wave impedance.
1 1
1
1
2
v
L
Z vZC
v Z
LC
Z
vLC
vZ
v
L
ZC
ZL
Cv Z
= =
=
=
=
= Ω
July, 2003 © 2003 by H.L. Bertoni 12
F(t-z/v) Is a Wave Traveling in +z Direction
Assume that
Then the voltage and current are
represents a wave disturbance
traveling in the positive direction with
velocity .
Note that the current in the conductor at
positive potential flows in the direction of
wave propagation.
G t z v
V z t F t z v F v z vt
I z tZ
F t z vZ
F v z vt
F t z v
z
v
( / )
( , ) ( / ) ( )( )
( , ) ( / ) ( )( )
( / )
+ =
= − = − −[ ]
= − = − −[ ]
−
0
1
1 11
V(z,0)=F[(-1/v)(z)]
V(z,t)=F[(-1/v)(z-vt)]
a z
-a
a+vt z
-a+vt
vt
t = 0
t > 0
July, 2003 © 2003 by H.L. Bertoni 13
G(t+z/v) Is a Wave Traveling in -z Direction
Assume that
Then the voltage and current are
represents a wave disturbance
traveling in the negative direction with
velocity .
Because of the minus sign in the
physical current in the conductor at positive
potential flows in the direction of wave propagation.
F t z v
V z t G t z v G v z vt
I z tZ
G t z vZ
G v z vt
G t z v
z
v
I z t
( / )
( , ) ( / ) ( )( )
( , ) ( / ) ( )( )
( / )
( , ),
− =
= + = +[ ]
=−
+ =−
+[ ]
+
0
1
1 11
V(z,0)=G[(1/v)(z)]
a 2a z
t = 0
V(z,t)=G[(1/v)(z+vt)]
2a-vt z
-vt
a-vt
t > 0
July, 2003 © 2003 by H.L. Bertoni 14
Example of Source ExcitationExcitation at one end of a semi - infinite length of transmission line.
Source has open circuit voltage and internal resistance
Radiation condition requires that excited waves travel away from source.
Terminal conditions at
or
V t R
z
V t R I t V t
RZ
F t F t
F tZ
Z RV t
V t R I t V t
RZ
G
S S
S S
S
SS
S S
S
( ) .
:
( ) ( , ) ( , )
( ) ( )
( ) ( )
( ) ( , ) ( , )
(
=
= +
= +
=+
= − +
= −−
0
0 0
1
0 0
1tt G t
G tZ
Z RV t
SS
) ( )
( ) ( )
+
=+
or
∞
z
VS(t) +
0
RS I(0,t)
V(0,t)
+ VS(t)
I(0,t) RS
V(0,t)
0 z
∞
July, 2003 © 2003 by H.L. Bertoni 15
Receive Voltage Further Along Line
+ VS(t)
∞
z
VS(t) +
0 l
RS
V(l,t)
Scope
RS
V(-l,t)
-l 0 z
∞
Scope
Voltage observed on a high impedance scope at a distance from source.
Delayed version of the source voltage
with the semi - infinite line acting as a
load resisor for the source.
Delayed version of the source voltage
with the semi - infinite line acting as a
load resisor for the source.
l
V l t F t l vZ
Z RV t l v
V l t G t l vZ
Z RV t l v
SS
SS
( , ) ( ) ( )
( , ) ( ) ( )
= − =+
−
− = + −[ ] =+
−
July, 2003 © 2003 by H.L. Bertoni 16
Power Carried by Waves
P(z,t)
I(z,t)
V(z,t)
z
Instantaneous power ( , ) carried past plane
perpendicular to .
The two waves carry power independently in the direction of wave
propagation
For each wave, a transmission line extending to acts as a resistor
of value Z, even though the wires were assumed to have no resistance.
P z t
z
P z t V z t I z t
F t z v G t z vZ
F t z v G t z v
ZF t z v G t z v
z
( , ) ( , ) ( , )
( ) ( ) ( ) ( )
( ) ( )
=
= − + +[ ] − − +[ ]
= − − +[ ]
→∞
1
1 2 2
July, 2003 © 2003 by H.L. Bertoni 17
Summary of Solutions for TL’s
• Solutions for V and I consists of the sum of thevoltages and current of two waves propagating in±z directions
• For either wave, the physical current flows in thedirection of propagation in the positive wire
• Semi-infinite segment of TL appears at itsterminals as a resistance of value Z (even thoughthe wires are assumed to have no resistance)
• The waves carry power independently in thedirection of wave propagation
July, 2003 © 2003 by H.L. Bertoni 18
Plane Waves in One Dimension
• Electric and magnetic fields in terms of voltageand current
• Maxwell’s equations for 1-D propagation
• Plane wave solutions
• Power and polarization
July, 2003 © 2003 by H.L. Bertoni 19
Electric Field and Voltage for Parallel Plates
The electric field goes from the positive plate to the negative plate. If
>> , the electric field outside of the plates is very small. Between
the plates it is nearly constant over the cross - section with value
Volts/m or
Recall that .
w h
E z th
V z t V z t hE z t
Cw
h
x x( , ) ( , ) ( , ) ( , ).= − = −
=
1
ε
w
h
z
y
Ex(z,t) + V(z,t)-
x
July, 2003 © 2003 by H.L. Bertoni 20
Magnetic Field and Current for Parallel Plates
w
h
z
y Hy(z,t) or By(z,t)
I(z,t)x
The magnetic field links the currents in the plates. If >> , the magnetic
field outside of the plates is very small. Between the plates it is nearly
constant over the cross - section, as if in a solenoid, with value
Amps/m or
Recall that .
w h
H z t B z tw
I z tw
I z t I z t wH z t
Lh
w
y y y( , ) ( , ) ( , ) ( , ) ( , ) ( , ).≡ = −
= − = −
=
1 1 1µ µ
µ
µ
July, 2003 © 2003 by H.L. Bertoni 21
Maxwell’s Equations in 1-D
Inserting the foregoing expressions for ( , ), , ( , ) and into the
Transmission Line equations
or
V z t C I z t L
zhE z t
h
w twH z t
zwH z t
w
h thE z t
zE z t
x y y x
x
∂∂
µ∂∂
∂∂
ε∂∂
∂∂
−[ ] = −
−[ ] −[ ] = −
−[ ]
= −
( , ) ( , ) ( , ) ( , )
( , ) µµ∂∂
∂∂
ε∂∂t
H z tz
H z tt
E z t
h w
x y
y y x( , ) ( , ) ( , )
These are the two Maxwell equations for linearly polarized wave propagating in
1- D. They are independent of ( , ) and refer to the fields.
We may think of the plates as being taken to ( , ) so they need not be
considered.
The field are in the form of a plane wave, which covers all space and is a simple
approximation for fields in a limited region of space, such as a laser beam.
= −
→∞
July, 2003 © 2003 by H.L. Bertoni 22
Plane Waves: Solutions to Maxwell Equations
Maxwell's equations are formally equivalent to the Transmission Line Equations
The solution is therefore in terms of two wave traveling in opposite directions
along .
In air 3 10 m/s is the speed of light and
is the wave impedance.
For waves in simple dielectric medium, is multiplied by the relative dielectric
constant
8
z
E z t F t z v G t z v H z t F t z v G t z v
v c
x y
o o
o
o
o
r
( , ) ( / ) ( / ) ( , ) ( / ) ( / )= − + + = − − +[ ]
= ≡ = × = =
1
1377
η
µ εη
µε
ε
ε
Ω
..
,
,
. .
For normal media but it can be a function of frequency. As and example,
in water at radio frequencies (below 20 GHz) but at optical
frequencies
ε
ε
ε
r
r
r
>
=
=
1
81
1 78
July, 2003 © 2003 by H.L. Bertoni 23
Power Density Carried by Plane Waves
Total instantaneous power carried in parallel plate line
watts
Power density crossing any plane perpendicular
to is
watt/m
2
P z t V z t I z t hE z t wH z t
hwE z t H z t
z
p z t P z t hw E z t H z t
F t z v
x y
x y
x y
( , ) ( , ) ( , ) ( , ) ( , )
( , ) ( , )
( , ) ( , ) ( , ) ( , )
( / )
= = −[ ] −[ ]=
= =
= −1 2
η−− +[ ]G t z v
H
E H
y
x y
2( / )
Direction of is such that turning a right hand screw in the
direction from to advances the screw in the direction of
propagation
E
Direction of
propagation
H
July, 2003 © 2003 by H.L. Bertoni 24
Polarization
The physical properties of a plane wave are independent of the
coordinate system.
For a plane wave traveing in one direction :
Electric field vector must be perpedicular to the direction of
propagation.
Magnetic field vector must be perpedicular to and to the
direction of propagation.
The vector cross product watt/m is in the direction
of propagation.
The ratio is the wave impedance
2
E
H E
p E H
E H
= ×
η.
July, 2003 © 2003 by H.L. Bertoni 25
Examples of Polarization
Linear polaization of along Linear polaization of along
E x E y
E a t z v E a t z v
H a t z v H a t z v
x y
y x
= −[ ] = −[ ]
= −[ ] = − −[ ]
cos ( / ) sin ( / )
cos ( / ) sin ( / )
ω ω
ηω
ηω
1 1
Circular polarization
E a t z v a t z v
H a t z v a t z v
x y
y x
= −[ ] + −[ ]
= −[ ] − −[ ]
cos ( / ) sin ( / )
cos ( / ) sin ( / )
ω ω
ηω ω
1
E
x z
H
y
x z
E
y H
a x
a yx
y
= unit vector along
= unit vector along
July, 2003 © 2003 by H.L. Bertoni 26
Summary of Plane Waves
• Plane waves are polarized with fields E and Hperpendicular to each other and to the direction ofpropagation
• Wave velocity is the speed of light in the medium
• ExH watts/m2 is the power density carried by aplane wave
July, 2003 © 2003 by H.L. Bertoni 27
Reflection and Transmission atJunctions
• Junctions between different propagation media• Reflection and transmission coefficients for 1-D
propagation• Conservation of power, reciprocity• Multiple reflection/transmission
July, 2003 © 2003 by H.L. Bertoni 28
Junctions Between Two Regions
0 z
I(0-,t) I(0+,t)
TL 1 V(0-,t) + V(0+,t) TL 2
Ex(0-,t) Ex(0+,t)
Hy(0-,t) Hy(0+,t)
Medium 1 Medium 2
x
z
Terminal condtions for the
Junction of two TL's
Boundary conditions at the
interface of two media
Plane wave propagation and
boundary conditions are analogus
to junctioning of two TL's
y y
V t V t
I t I t
E t E t
H t H t
x x
( , ) ( , )
( , ) ( , )
( , ) ( , )
( , ) ( , )
0 0
0 0
0 0
0 0
− +
− +
− +
− +
=
=
=
=
July, 2003 © 2003 by H.L. Bertoni 29
Reflection and Transmission
Incident wave
ExIn(z,t)=F1(t-z/v1)
HyIn(z,t) Transmitted wave
Reflected wave
v1 and η1 v2 and η2
x
z
A source creates an incident wave whose electric field is given by the known
function (t - z/v ). Using the boundary conditions we solve for the unknown
functions (t +z/v ) and (t - z/v ) for the electric fields of the reflected
and transmitted waves : (t) +G (t) (t)
(t) - G (t) (t)
1
1 2
1
1
F
G F
E t F F E t
H t F F H t
x x
y y
1
1 2
1 2
11
22
0 0
01 1
0
( , ) ( , )
( , ) ( , )
− +
− +
= = =
= [ ] = =η η
July, 2003 © 2003 by H.L. Bertoni 30
Reflection and Transmission Coefficients
Solution of the boundary condition equations for and in terms of
The reflection coefficient and transmission coefficient are given by :
Examples :
I. Suppose medium 1 is air so that 377 and medium 2 has
relative dielectric constant
G t F t F t
G t F t F t F t
o o
r
1 2 1
1 1 2 1
2 1
2 1
2
2 1
1
12
( ) ( ) ( )
( ) ( ) ( ) ( )= =
=−+
= + =+
= ≡ =
=
Γ Τ
Γ Τ
Γ Τ Γη ηη η
ηη η
η η µ ε
ε 44 0 5
0 50 5
13
113
23
2 so that Then going
from air - to - dielectric and
η µ ε ε η
η ηη η
= =
=−+
= − = − =
o r o
ad ad
. .
.
.Γ Τ
July, 2003 © 2003 by H.L. Bertoni 31
Reflection and Transmission, cont.
II. Now suppose the wave is incident from the dielectric onto air so that medium 1
is the dielectric and medium 2 is air Then going from
dielectic - to - air, and
Note that :
1.
2. Since T is the ratio of fields, not power, it can be greater than 1.
2η η η η
η ηη η
1 0 5
0 50 5
13
113
43
=( ) =( )
=−+
= + = + =
= −
. .
.
.Γ Τ
Γ Γ
da ad
da ad
July, 2003 © 2003 by H.L. Bertoni 32
Reflected and Transmitted Power
Instantaneous power carried by the incident wave the reflected wave
, and the transmitted wave
p z t
p z t p z t
p z t E z t H z t F t z v
p z t E z t H z t G t z v
p
In
Tr
InxIn
yIn
x y
Tr
( , ),
( , ) ( , )
( , ) ( , ) ( , ) ( )
( , ) ( , ) ( , ) ( )
(
Re
Re Re Re
= = −
= =−
+
1
11
12
1
112
1
η
η
zz t E z t H z t F t z v
p tZ
F t
p t G t F t p t F t F
xTr
yTr
In
Tr
, ) ( , ) ( , ) ( )
( , ) ( )
( , ) ( ) ( ) ( , ) ( )Re
= = −
=
= = = =
−
− +
1
01
01 1
01 1
222
1
112
112 2
112
222 2
2
η
η η η η
Just on either side of the interface as well as
and Γ Τ 112( )t
July, 2003 © 2003 by H.L. Bertoni 33
Conservation of Power and Reciprocity
Conservation of power requires that so that
or 1
This relation is easily shown to be satisfied from the expressions for , .
For waves going from medium 2 to medium 1, the reflection coefficient is
the negative of going from medium 1 to medium 2. Thus for either
case the ratios
21
p t p t p t
F t F t F t
p t
p
In Tr( , ) ( , ) ( , )
( ) ( ) ( )
( , )
Re
Re
0 0 0
1 1 1
0
11
2 2
11
2 2
21
2 2 2 1
2
12
− − +
−
− =
− = − =η η η
ηη
Γ Τ Γ Τ
Γ Τ
Γ
Γ
InIn
Tr
Int
p t
p t( , )( , )( , )000
2 2−
+
−= = −Γ Γ and 1 are the same.
Therefore the same fraction of the incident power is reflected from and
transmitted through the interface for waves incident from either medium.
This result is an example of a very general wave property called reciprocity.
July, 2003 © 2003 by H.L. Bertoni 34
Termination of a Transmission Line
I(0-,t)
TL V(0-,t) + RL
0 z
Terminal condtions
Solving for ( ) in terms of ( ),
( ) where the reflection
coefficient is
Special cases :
1. Matched termination, and Simulates a semi - infinite TL
2. Open circuit, and Total reflection with
V t R I t
F t G tR
ZF t G t
G t F t
G t F t
R Z
R Z
R Z
R V
L
L
L
L
L
L
( , ) ( , )
( ) ( ) ( ) ( )
( )
.
. ( ,
0 0
0
1 0
=
+ = −
=
=−+
= =
→∞ =
Γ
Γ
Γ
Γ tt F t
R V tL
) ( ).
. ( , ) .
=
= = − =
2
0 1 0 0 3. Short circuit, and Total reflection with Γ
July, 2003 © 2003 by H.L. Bertoni 35
Reflections at Multiple Interfaces
Incident wave
ExIn(z,t)=F1(t-z/v1)
TransmittedHy
In (z,t) waves
Reflected waves Multiple
internal reflections
v1 and η1 v2 and η2 v3 and η3
x
0 l z
Multiple internal reflections occur within the finite thickness layer. These
internal waves generate multiple reflected waves in medium 1 and multiple
transmitted waves in medium 3.
July, 2003 © 2003 by H.L. Bertoni 36
Scattering Diagram for a Layer
1
Γ12
Τ12 Γ23 Τ21
Τ12 (Γ23)2 Γ21 Τ21
Τ12Τ23
Τ12 Γ23 Γ21 Τ23
Τ12 (Γ23)2 (Γ21)2 Τ23
l z
2l/v2
4l/v2
t
Τ12
Τ12 Γ23
Τ12 Γ23 Γ21
Τ12 (Γ23)2 Γ21
Τ12 (Γ23)2 (Γ21)2
Τ12 (Γ23)3 (Γ21)2
Space - time diagram indicates the relative amplitudes of the electric field of
the individual components of the multiply reflected waves. In adding fields,
account must be taken of the relative delay between the different components.
July, 2003 © 2003 by H.L. Bertoni 37
Summary of Reflection and Transmission
• The planar interface between two media is analogous to thejunction of two transmission lines
• At a single interface (junction) the equation T = 1 + Γ is astatement of the continuity of electric field (voltage)
• The ratio of reflected to incident power = Γ2
• Power is conserved so that the ratio of transmitted to incidentpower = 1 - Γ2
• The reciprocity condition implies that reflected and transmittedpower are the same for incidence from either medium
• At multiple interfaces, delayed multiple interactions complicatethe description of the reflected and transmitted fields forarbitrary time dependence
July, 2003 © 2003 by H.L. Bertoni 38
Spatial Variations for HarmonicTime Dependence
• Traveling and standing wave representations ofthe z dependence
• Period average power
• Impedance transformations to account for layeredmaterials
• Frequency dependence of reflection from a layer
July, 2003 © 2003 by H.L. Bertoni 39
Harmonic Time Dependence at z = 0
Suppose that the voltage and current (or and fields) have harmonic time
dependence ( ) at Then
where and are the complex voltage and current at .
The functions and can satisfy these equations only if they too have
E H
j t z
V t V e F t G t
I t I eZ
F t G t
V I z
F t G t
x y
j t
j t
exp .
( , ) ( ) ( ) ( )
( , ) ( ) ( ) ( )
( ) ( )
( ) ( )
ωω
ω
=
= = +
= = −[ ]
=
0
0 0
0 01
0 0 0
harmonic time dependence. Hence harmonic time dependence. Hence
( ) and G(t) =
where and are the complex
voltage amplitudes of the waves traveling in the directions.
F t V e V e
V V ZI V V ZI
z
j t j t=
= +[ ] = −[ ]±
+ −
+ −
ω ω
12
120 0 0 0( ) ( ) ( ) ( )
July, 2003 © 2003 by H.L. Bertoni 40
Traveling Wave Representation
At other locations
z
V z t F t z v G t z v V j t z v V j t z v
V e V e e V z e
I z tZ
F t z v G t z v
j z v j z v j t j t
≠
= − + + = −[ ] + +[ ]= + =
= − − + =
+ −
+ − − +
0
1
( , ) ( ) ( ) exp ( ) exp ( )
( )
( , ) ( ) ( )
ω ωω ω ω ω
11
1
1
ZV j t z v V j t z v
ZV e V e e I z e
V z I z
j t
k v
V z V
j z v j z v j t j t
+ −
+ − − +
−
+
−[ ] − +[ ]
= − =
≡
=
exp ( ) exp ( )
( )
( ) ( )
exp
.
( )
ω ω
ω
ω
ω ω ω ω
Here is the phasor voltage and is the phasor current, which give the
spatial variation for the implied time dependence ( ).
Define the wave number (propagation constant) m Then
ee V e I zZ
V e V ejkz jkz jkz jkz− − + + − − ++ = − and
is the traveling wave representation of phasor voltage and current.
( )1
July, 2003 © 2003 by H.L. Bertoni 41
Standing Wave Representation
Substituting the expressions for and in terms of and ( ),
and rearranging terms gives the standing wave representation of the phasor
voltage and current :
V V V I
V z V e e ZI e e V kz jZI kz
I zZ
V e e I e e
jkz jkz jkz jkz
jkz jkz jkz
+ −
− + − +
− + − +
= +[ ] + −[ ] = −
= −[ ] + +
( )
( ) ( ) ( ) ( )cos ( )sin
( ) ( ) ( )
0 0
0 0 0 0
0 0
12
12
12 1
2jkzjkz I kz j
ZV kz[ ] = −( )cos ( )sin0
10
The wavenumber is where is the
wavelength 2 k
For plane waves in a dielectric medium
k v f v
v f
k
= = =
= =
=
ω π π λ λ
λ π
ω µε
2 2
July, 2003 © 2003 by H.L. Bertoni 42
Variation of the Voltage Magnitude
For we have a pure traveling
wave . The magnitude
= is independent
of
V
V z V e
V z V e V
z
jkz
jkz
−
+ −
+ − +
=
=
=
0
( )
( )
.
|V+|
z
V z( )
For (0) we have a pure standing
wave . Its magnitude
cos is periodic with
period 2.
I
V z V kz
V z V kz
k
=
=
=
=
0
0
0
( ) ( )cos
( ) ( )
π λ
0 λ/2 z
V z( )
V ( )0
July, 2003 © 2003 by H.L. Bertoni 43
Standing Wave Before a Conductor
ISC
η, v short
0 z
Incident wave
ExIn(z)
HyIn(z)
ExRe(z)
Reflected wave
x
Perfect
conductor
0 z
Plane wave incident on a perfectly
conduticng plate and the equivalent
circuit of a shorted TL
and
The standing wave field is
Two waves of equal amplitude and
traveling in opposite directions create
a standing wave.
E H I
E z I e e
j I kz
x y SC
x SCjkz jkz
SC
( ) ( )
( )
sin
0 0 0
12
= =
= −[ ]= −
− +η
η
July, 2003 © 2003 by H.L. Bertoni 44
Standing Wave Before a Conductor, cont.
Plot of the magnitude of the standing wave field
E z I kzx SC( ) sin=η
Since the nodes (zeros) of the field are
separated by a distance or
k v f v
k z z k
= = =
= = =
ω π π λ
π π λ
2 2
2∆ ∆
ηISC
-λ −3λ/4 −λ/2 −λ/4 0 z
July, 2003 © 2003 by H.L. Bertoni 45
Period Averaged Power
For harmonic time dependence on a TL, the time average over one period
of the instantaneous power is watts
Using the traveling wave representation
Note that the average power is the algebraic sum of the power carried by
the incident and reflected waves, and it is independent of
For harmonic plane waves
P z V z I z
P z V e V eZ
V e V eZ
V V
z
p z E
jkz jkz jkz jkz
x
( ) Re ( ) ( )
( ) Re
.
( ) Re (
=
= +[ ] −[ ]
= −
=
∗
+ − − + + − − + ∗ + −
12
12
2 2
12
1 12
zz H z
p z E E
y
xIn
x
) ( )
( ) Re
∗ = −
watts/m
In terms of traveling waves
2
12
2 2
η
July, 2003 © 2003 by H.L. Bertoni 46
Reflection From a Load Impedance
V+
V- ZL
0 z
I(0)
V(0) + ZL
0 z
For a complex load impedance
Solving for in terms of gives
where the complex
reflection coefficient is
Reflected power
Z
V V V Z IZ
ZV V
V V
V V
Z Z
Z Z
PZ
VZ
V P
L
LL
L
L
In
( ) ( )
Re
0 0
12
12
2 2 2
= + = = −( )
=
=−+
= = =
+ − + −
− +
− +
− +
Γ
Γ
Γ
Γ Γ
July, 2003 © 2003 by H.L. Bertoni 47
Summary of Spatial Variation for HarmonicTime Dependence
• Field variation can be represented by two traveling wavesor two standing waves
• The magnitude of the field for a pure traveling wave isindependent of z
• The magnitude of the field for a pure standing wave isperiodic in z with period λ/2
• The period average power is the algebraic sum of thepowers carried by the traveling waves
• The period average power is independent of z no matter ifthe wave is standing or traveling
• The fraction of the incident power carried by a reflectedwave is |Γ|2
July, 2003 © 2003 by H.L. Bertoni 48
Impedance Transformationsin Space
• Impedance variation in space
• Using impedance for material layers
• Frequency dependence of reflection from a brickwall
• Quarter wave matching layer
July, 2003 © 2003 by H.L. Bertoni 49
Defining Impedance Along a TL
I(0)
ZIN V(0) + ZL
-l 0 z
At the ratio of voltage to current
can have some value ( )
Using the formulas for and
we can compute their ratio at
Defining this ratio as we have
( ) (-
(- ( ) (- )
Dividing numerator and denominator by and rearranging gives
z
V I Z
V z I z
z l
Z l
Z lV l
I l
V kl jZI kl
I kl jZ
V kl
I
L
IN
IN
=
≡
= −
≡−−
=− −
−
0
0 0
0 0
01
0
0
( )
( ) ( )
.
( )
( )( )( )
cos ) ( )sin( )
( )cos ) sin
( )
(
( ( ) ( )Z l Z
Z kl jZ kl
Z kl jZ klZ
Z jZ kl
Z jZ klINL
L
L
L
( )cos ) sin( )
cos ) sintan( )tan
=+
+=
++
July, 2003 © 2003 by H.L. Bertoni 50
Properties of the Impedance Transform
The impedance formula
(
( ( ) ( )
shows that a length TL (or region of space) transforms an impedance
to a different value.
Some properties of the transformation :
1. For a matched load the imput impedace is matched
2. The impedance repeats for or
Z l ZZ kl jZ kl
Z kl jZ klZ
Z jZ kl
Z jZ kl
Z Z Z Z
Z l Z l l k l
l k
INL
L
L
L
L IN
IN IN
( )cos ) sin( )
cos ) sintan( )tan
,
( ) ( )
=+
+=
++
= =
= + =
= =
∆ ∆
∆
π
π λ 2
3. For quarter wave displacement 3. For quarter wave displacement and impedance
inverts
4. If then
l kl
Z Z Z
Z Z l jZ klIN L
L IN
= =
=
= =
λ π
λ
4 2
4
0
2
,
( )
, ( ) tan( )
July, 2003 © 2003 by H.L. Bertoni 51
Using Transform for Layered Media
Incident wave
ExIn(z) Ex
TR(z) Transmitted
HyIn (z) wave
ExRe(z)
Reflected wave
v1 , η1 v2 , η2 v3 , η3
x
0 l z
ZIN(l) ZL = η3
Z= η2
July, 2003 © 2003 by H.L. Bertoni 52
Circuit Solution for Reflection Coefficient
Medium 3 acts as a load on the layer to the left. A semi- infinite TL (medium)
at its terminals (accessible surface) acts as a resistor so that
Impedance of the finite segment of TL is . Wavenumber of this
segment is
where is the wavenumber of free space.
Input impedance at left surface of the layer is then
(( ( )
Z
Z
k v k
k
Z lk l j k l
k l j k l
L
r o o o r
o o o
IN
=
=
= = =
=
=++
η
η
ω ω ε ε µ ε
ω ε µ
ηη ηη η
3
2
2 2 2 2
23 2 2 2
2 2 3 2
.
( )cos ) sin( )cos ) sin
Reflection coefficient for the wave incident from medium 1 is Reflection coefficient for the wave incident from medium 1 is
(
(Γ =
−+
=−( ) + −
+( ) + +Z l
Z l
k l j k l
k l j k lIN
IN
( )( )
cos ) ( )sin( )
cos ) ( )sin( )ηη
η η η η ηηη η η η ηη
1
1
2 3 1 2 22
1 3 2
2 3 1 2 22
1 3 2
July, 2003 © 2003 by H.L. Bertoni 53
Example 1: Reflection at a Brick Wall
H yIN
E xIN
w
Medium 1 and medium 3 are air
Medium 2 is brick with
and
η η ηµε
ε
ηµε ε
η
1 3
2
2 22
12
4
2
= = ≡
≈
= = =
oo
o
r
oo
r ook k
Reflection coefficient for the wave incident from air is
(
(
Γ =−( ) + −
+( ) + +
=−( )+ +( )
η η η η ηηη η η η ηη
η η
η η η
2 3 1 2 22
1 3 2
2 3 1 2 22
1 3 2
14
2 2
2 14
2 2
2
2 2
cos ) ( )sin( )
cos ) ( )sin( )
sin( )
cos( ) sin(
k w j k w
k w j k w
j k w
k w jo o o
o o o o 22
2
2 2 2
34
54k w
j k w
k w j k wo
o
o o)
sin( )
cos( ) sin( )=
+
July, 2003 © 2003 by H.L. Bertoni 54
Example 1: Reflection at a Brick Wall, cont.
Let the wall thickness be cm so that
Then
w k wf
f
p pf
f f
o GHz
in GHz
GHz GHz
= =×
=
= =+
30 24
3 100 3 4
9 4
64 4 25 4
8
22
2 2
ππ
ππ π
.
sin ( )
cos ( ) sin ( )Re Γ
Since there is no conductivity in the brick wall, the fraction of the incident
power transmitted through the wall is 2
1− Γ
0 0.25 0.50 0.75 1.0 1.25 1.50 1.75 2.0 fGHz
|Γ|2
9/25
July, 2003 © 2003 by H.L. Bertoni 55
Example 2: Quarter Wave Layers
Incident wave
ExIn(z) Ex
TR(z) Transmitted
HyIn (z) wave
ExRe(z)
Reflected wave
v1 , η1 v2 , η2 v3 , η3
l=π/(2k2)=λ2/4
x
0 z
cos( ) cos( ) cos( / ) ( ) sin( / )
( / ) /
k l k k l
ZIN
2 2 2 2
2 22
3
4 2 0 2 1
4
= = = = =
=
λ π π
λ η η
and sin
so that
July, 2003 © 2003 by H.L. Bertoni 56
Example 2: Quarter Wave Layers, cont.
For this value of we have
If we choose the layer material such that then and no
reflection takes place.
Suppose that medium 1 is air and medium 3 is glass with relative
dielectric constant
For no reflection : or
Note that the layer thickness is
g
Z
lv
f f
IN
o
r o
o
o
o
g or g
r o o
Γ
Γ
=−+
= =
= = = =
= = =
η ηηη ηη
η ηη
ε
ηµε ε
ηηµε
µε ε
ε ε
λε ε µ
22
1 3
22
1 3
22
1 3
22
21 3 2
22
2
0
44
1
4
,
/ ==
=
v
f
l
o
r
o
g
o
4
4
2
4
ε
λε
λ or where is the wavelength in air.
July, 2003 © 2003 by H.L. Bertoni 57
Summary of Impedance Transformation
• The impedance repeats every half wavelength inspace, and is inverted every quarter wavelength
• Impedances can be cascaded to find the impedanceseen by an incident wave
• Reflection from a layer has periodic frequencydependence with minima (or maxima) separatedby ∆f = v2/(2w)
• Quarter wave layers can be used impedancematching to eliminate reflections
July, 2003 © 2003 by H.L. Bertoni 58
Effect of Material Conductivity
• Equivalent circuit for accounting for conductivity
• Conductivity of some common dielectrics
• Effect of conductivity on wave propagation
July, 2003 © 2003 by H.L. Bertoni 59
G, C, L for Parallel Plate Line
w
h
z
If the material between the plate conducts electricity, there will be a
conductance mho/m in addition to the capacitance farads/m
and inductance henry/m.
The conductivity of a material is give by the parameter mho/m
Expressions for the circuit quantities are :
G C
L
Gw
hC
w
hL
h
w
σ
σ ε µ= = =
July, 2003 © 2003 by H.L. Bertoni 60
Equivalent Circuit for Harmonic Waves
In the limit as the Kirchhoff circuit equations for the phasor
voltage and current give the TL equations for harmonic time dependence
∆z
dV z
dzj LI z
dI z
dzG j C V z
→
= − = − +( )
0
( )( )
( )( )ω ω
+
I(z) V(z)
-z z+∆z z
I(z) +
V(z)
+ I(z +∆z)
V(z+∆z)jωL∆z jω C ∆z G
July, 2003 © 2003 by H.L. Bertoni 61
Harmonic Fields and Maxwell’s Equations
If >> , the fields between the plates are nearly constant over the cross- section,
so that the phasor circuit quantities are and
Substituting these exprsssions in the TL equations for harmonic time dependence,
along with the expressions for , , gives Maxwell's equations
w h
V z hE z I z wH z
G C L
dE z
dzj H z
dH z
dzj E z
x y
xy
yx
( ) ( ) ( ) ( ).
( )( )
( )( )
= − = −
= − = − +( )ωµ ωε σ
w
h
z
y Hy(z)
I(z)x +
V(z)
Ex(z)
July, 2003 © 2003 by H.L. Bertoni 62
Maxwell’s Equations With Medium Loss
With minor manipulation, Maxwell's equations for 1- D propagation of
harmonic waves in a medium with conduction loss can be written
and
The complex equivalent dielectric constant is given by
Let " Then "
In other matierials atomic processes lead to a complex dielectric of the
form
o o o
o r
dE z
dzj H z
dH z
dzj E z
j j
j
xy
yx
r r
o
( )( )
( ) ˆ ( )
ˆ
ˆ
. ˆ
= − = −
= − = −( )= = −( )
ωµ ωε
ε
ε ε ε σ ω ε ε σ ωε
ε σ ωε ε ε ε ε
εε ε ε
εo jr " These processes have a different frequency
dependence for ", but have the same effect on a hamonic wave
−( ).
July, 2003 © 2003 by H.L. Bertoni 63
Constants for Some Common Materials
When conductivity exists, use complex dielectric constant given by
ε = εo(εr - jε") where ε" = σ/ωεo and εo ≈ 10-9/36π
Material* εr σ (mho/m) ε" at 1 GHz
Lime stone wall 7.5 0.03 0.54Dry marble 8.8 0.22Brick wall 4 0.02 0.36Cement 4 - 6 0.3Concrete wall 6.5 0.08 1.2Clear glass 4 - 6 0.005 - 0.1Metalized glass 5.0 2.5 45Lake water 81 0.013 0.23Sea Water 81 3.3 59Dry soil 2.5 -- --Earth 7 - 30 0.001 - 0.03 0.02 - 0.54
* Common materials are not well defined mixtures and often contain water.
July, 2003 © 2003 by H.L. Bertoni 64
Incorporating Material Loss Into Waves
Using the equivalent complex dielectric constant, Maxwell's equations
have the same form as when no loss (conductivity) is present.
The solutions therefore have the same mathematical form with
replaced by
For example, the traveling wave solutions in a material are
and
Here and
are complex quantities.
ε
ε
η
ω µε ω µε ε ε ηµε
µε ε ε
ˆ.
( ) ( )
ˆ "ˆ "
E z V e V e H z V e V e
k jj
xjkz jkz
yjkz jkz
o ro r
= + = −
= = −( ) = =−( )
+ − − + + − − +1
July, 2003 © 2003 by H.L. Bertoni 65
Wave Number and Impedance
The complex wavenumber will have real and imaginary parts
If is less than about we may use the approximations
and
Similarly, for small,
k
k j j
jj
o r
r
o r o rr
o r o r r
≡ − = −( )
≈ ≈
=−( )
≈ +
β α ω µε ε ε
ε ε
β ω µε ε α ω µε εεε
ε ηµ
ε ε εµε ε
εε
"
" ,
"
""
"
10
2
12
July, 2003 © 2003 by H.L. Bertoni 66
Effect of Loss on Traveling Waves
For a wave traveling in the positive direction
(-
The presence of loss (conductivity) results in a finite value of the
attenuation constant . The attenuation (decay) length is 1 .
The magnitude of the field depends on z as given by
z
E z V e V j j z V j z z
E z V z
xjkz
x
( ) exp ( ) exp )exp( )
( ) exp( )
= = − −[ ] = −
= −
+ − + +
+
β α β α
α α
α
|V+|
|V+| /e
1/α z
July, 2003 © 2003 by H.L. Bertoni 67
Attenuation in dB
For a traveling wave, the attenuation in units of deci - Bells is found from
Thus the attenuation rate of the wave in a medium is dB/m
AttnE z
E
V z
V
z e z
x
x
= −
= −
−
= =
+
+20
020
20 8 67
8 67
10 10
10
log( )
( )log
exp( )
log .
.
α
α α
α
July, 2003 © 2003 by H.L. Bertoni 68
Effect of Loss on Traveling Waves, cont.
The instantaneous field of the wave has both sinusoidal variation over a
wavelength and the decay over the attenuation length 1 .
For real amplitude , the spatial variation is given by
Re
or
os( t -
λ π β α
ω β α
ω β α
ω
=
= −[ ] −
−
+
+
+
2
V
E z e V j t z z
V c z z
xj t( ) Re exp ( ) exp( )
)exp( )
1/α
λ=2π/β
V+
V+/e z
July, 2003 © 2003 by H.L. Bertoni 69
Loss Damps Out Reflection in Media
Traveling waveamplitude
z
Reflectingboundary
Incident wave
Reflected wave
E z V z E z V zxIN
x( ) exp( ) ( ) exp( )Re
= − = ++ +α αΓ
July, 2003 © 2003 by H.L. Bertoni 70
Effect of Damping on the |Γ| for a Wall
0 0.25 0.50 0.75 1.0 1.25 1.50 1.75 2.0 fGHz
|Γ|2
9/25
1/9
With absorption in the brick wall, the interference minima are
reduced and the reflection coefficient approaches that of the
first air - brick interface or
The fraction of the incident power transmitted through the
wall is 2
Γ
Γ
=−+
= −
≠ −
η ηη η
B o
B o
1 3
1
July, 2003 © 2003 by H.L. Bertoni 71
Summary of Material Loss
• Conductivity is represented in Maxwell’s equationsby a complex equivalent dielectric constant
• The wavenumber k = β − jα and wave impedanceη then have imaginary parts
• The attenuation length = 1/α
• Loss in a medium damps out reflections within amedium