©1989 Burr-Brown Corporation PDS-1026E Printed in U.S.A. February, 1995

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High Speed, Current-Feedback, High VoltageOPERATIONAL AMPLIFIER

FEATURES WIDE SUPPLY RANGE: ±4.5 to ±18V

BANDWIDTH: 100MHz, G = 1 to 10

SLEW RATE: 1000V/ µs

FAST SETTLING TIME: 50ns to 0.1%

HIGH OUTPUT CURRENT: ±150mA peak

HIGH OUTPUT VOLTAGE: ±12V

DESCRIPTIONThe OPA603 is a high-speed current-feedback op ampwith guaranteed specifications at both ±5V and ±15Vpower supplies. It can deliver full ±10V signals into150Ω loads with up to 1000V/µs slew rate. Thisallows it to drive terminated 75Ω cables. With 150mApeak output current capability it is suitable for drivingload capacitance or long lines at high speed.

In contrast with conventional op amps, the current-feedback approach provides nearly constant band-width and settling time over a wide range of closed-loop voltage gains.

The OPA603 is available in a plastic 8-pin DIP andSO-16 surface-mount packages, specified over theindustrial temperature range.

APPLICATIONS VIDEO AMPLIFIER

PULSE AMPLIFIER

SONAR, ULTRASOUND BUFFERS

ATE PIN DRIVERS

xDSL LINE DRIVER

FAST DATA ACQUISTION

WAVEFORM GENERATORS

–VS

4

+In

3

+VS

7

VO

6

–In

2

® OPA603OPA603

OPA603

®

OPA603 2

OPA603AP, AU

PARAMETER CONDITIONS MIN TYP MAX UNITS

INPUT OFFSET VOLTAGEInitial 5 mV

vs Temperature 8 µV/°Cvs Common-Mode Voltage VCM = ±10V 50 60 dBvs Supply (tracking) Voltage VS = ±12V to ±18V 80 85 dBvs Supply (non-tracking)(1) |VS| = 12V to 18V 55 60 dB

+INPUT BIAS CURRENTInitial 5 µA

vs Temperature 30 nA/°Cvs Common-Mode VCM = ±10V 200 500 nA/Vvs Supply (tracking) VS = ±12V to ±18V 50 100 nA/Vvs Supply (non-tracking)(1) |VS| = 12V to 18V 150 300 nA/V

–INPUT BIAS CURRENTInitial 25 µA

vs Temperature 300 nA/°Cvs Common-Mode VCM = ±10V 200 600 nA/Vvs Supply (tracking) VS = ±12V to ±18V 300 500 nA/Vvs Supply (non-tracking)(1) |VS| = 12V to 18V 1500 2000 nA/V

INPUT IMPEDANCE+Input 5 || 2 MΩ || pF–Input 30 || 2 Ω || pF

OPEN LOOP CHARACTERISTICSTransresistance VO = ±10V 300 440 kΩTranscapacitance 1.8 pF

OUTPUT CHARACTERISTICSVoltage RL = 150Ω ±10 ±12 VPeak Current 150 mAShort-Circuit Current(2) VO = 0V 250 mAOutput Resistance, Open-Loop 70 Ω

FREQUENCY RESPONSE G = +2Small-Signal Bandwidth(3) 70 160 MHz

Gain Flatness, ±0.5dB 35 75 MHzFull-Power Bandwidth VO = 20Vp-p 10 MHzDifferential Gain f = 4.43MHz, VO = 1V 0.03 %Differential Phase f = 4.43MHz, VO = 1V 0.025 Degrees

TIME DOMAIN RESPONSE G = +2Propagation Delay 10 nsRise and Fall Time 10 nsSettling Time to 0.10% 10V Step 50 nsSlew Rate 1000 V/µs

DISTORTION G = +2, RL = 100Ω, f = 10MHz2nd Harmonic Distortion VO = 0.2Vp-p –60 –65 dBc3rd Harmonic Distortion VO = 0.2Vp-p –70 –90 dBc

POWER SUPPLYSpecified Operating Voltage ±15 VOperating Voltage Range ±4.5 ±18 VCurrent ±21 ±25 mA

TEMPERATURE RANGESpecification –25 +85 °CStorage –40 +150 °C

THERMAL RESISTANCE, θJA Soldered to Printed Circuit 90 °C/W

SPECIFICATIONS: VS = ±15VELECTRICALAt T

A = +25°C, and R

L = 150Ω, unless otherwise noted.

NOTES: (1) One power supply fixed at 15V; the other supply varied from 12V to 18V. (2) Observe power derating curve. (3) See bandwidth versus gain curve,Figure 5.

The information provided herein is believed to be reliable; however, BURR-BROWN assumes no responsibility for inaccuracies or omissions. BURR-BROWN assumesno responsibility for the use of this information, and all use of such information shall be entirely at the user’s own risk. Prices and specifications are subject to changewithout notice. No patent rights or licenses to any of the circuits described herein are implied or granted to any third party. BURR-BROWN does not authorize or warrantany BURR-BROWN product for use in life support devices and/or systems.

®

OPA6033

OPA603AP, AU

PARAMETER CONDITIONS MIN TYP MAX UNITS

INPUT OFFSET VOLTAGEInitial 6 mV

vs Temperature 8 µV/°Cvs Common-Mode VCM = ±3V 50 55 dBvs Supply (tracking) VS = ±4V to ±6V 75 80 dBvs Supply (non-tracking)(1) |VS| = 4V to 6V 55 60 dB

+INPUT BIAS CURRENTInitial 5 µA

vs Temperature 30 nA/°Cvs Common-Mode VCM = ±3V 350 600 nA/Vvs Supply (tracking) VS = ±4V to ±6V 100 200 nA/Vvs Supply (non-tracking)(1) |VS| = 4V to 6V 200 300 nA/V

–INPUT BIAS CURRENTInitial 25 µA

vs Temperature 300 nA/°Cvs Common-Mode VCM = ±3V 300 600 nA/Vvs Supply (tracking) VS = ±4V to ±6V 500 700 nA/Vvs Supply (non-tracking)(1) |VS| = 4V to 6V 2500 3000 nA/V

INPUT IMPEDANCE+Input 3.3 || 2 MΩ || pF–Input 30 || 2 Ω || pF

OPEN LOOP CHARACTERISTICSTransresistance VO = ±2V 225 330 kΩTranscapacitance 2.4 pF

OUTPUT CHARACTERISTICSVoltage RL = 75Ω ±2 ±2.75 VPeak Current 150 mAShort-Circuit Current(2) VO = 0V 250 mAOutput Resistance, Open-Loop 80 Ω

FREQUENCY RESPONSE G = +2Small-Signal Bandwidth(3) 140 MHz

Gain Flatness, ±0.5dB 65 MHzFull-Power Bandwidth 20 MHzDifferential Gain f = 4.43MHz, VO = 1V, RL = 150Ω 0.03 %Differential Phase f = 4.43MHz, VO = 1V, RL = 150Ω 0.025 Degrees

TIME DOMAIN RESPONSE G = +2, RL = 100ΩPropagation Delay 15 nsRise and Fall Time 20 nsSettling Time to 0.10% 60 nsSlew Rate 750 V/µs

DISTORTION G = +2, RL = 100Ω, f = 10MHz2nd Harmonic Distortion VO = 0.2Vp-p –67 dBc3rd Harmonic Distortion VO = 0.2Vp-p –78 dBc

POWER SUPPLYSpecified Operating Voltage ±5 VOperating Voltage Range ±4.5 ±18 VCurrent ±21 ±25 mA

TEMPERATURE RANGESpecification –25 +85 °CStorage –40 +150 °C

THERMAL RESISTANCE, θJUNCTION-AMBIENT Soldered to Printed Circuit 90 °C/W

SPECIFICATIONS: VS = ±5VELECTRICALAt T

A = +25°C, and R

L= 75Ω, unless otherwise noted.

NOTES: (1) One power supply fixed at 5V; the other supply varied from 4V to 6V. (2) Observe power derating curve. (3) See bandwidth versus gain curves,Figure 5.

®

OPA603 4

Top View DIP

PIN CONFIGURATION

Top View SO-16

1

2

3

4

5

6

7

8

NC

NC

–In

NC

+In

NC

–VS

NC

NC: No Internal Connection.Solder to ground plane forimproved heat dissipation.

16

15

14

13

12

11

10

9

NC

NC

+VS

NC

VO

NC

NC

NC

PIN CONFIGURATION

1

2

3

4

8

7

6

5

NC

–In

+In

–V

NC

+V

V

NC

S

S

NC: No Internal Connection.Solder to ground plane forimproved heat dissipation.

O

PACKAGE/ORDERING INFORMATION

PACKAGE SPECIFIEDDRAWING TEMPERATURE

PRODUCT PACKAGE NUMBER (1) RANGE

OPA603AP Plastic DIP 006 –25°C to +85°COPA603AU SO-16 211 –25°C to +85°C

NOTE: (1) For detailed drawing and dimension table, please see end of datasheet, or Appendix C of Burr-Brown IC Data Book.

ABSOLUTE MAXIMUM RATINGS

Supply Voltage ................................................................................... ±18VInput Voltage Range ............................................................................ ±VS

Differential Input Voltage ..................................................................... ±6VPower Dissipation ........................................................ See derating curveOperating Temperature ................................................................. +100°CStorage Temperature ..................................................................... +150°CJunction Temperature .................................................................... +150°CLead Temperature (soldering, 10s) ............................................... +300°C

(soldering SO-16 package, 3s) ...................... +260°C

ELECTROSTATICDISCHARGE SENSITIVITY

This integrated circuit can be damaged by ESD. Burr-Brownrecommends that all integrated circuits be handled withappropriate precautions. Failure to observe proper handling andinstallation procedures can cause damage.

ESD damage can range from subtle performance degradation tocomplete device failure. Precision integrated circuits may be moresusceptible to damage because very small parametric changescould cause the device not to meet its published specifications.

®

OPA6035

TYPICAL PERFORMANCE CURVESAt TA = +25°C, unless otherwise noted.

OUTPUT SWING vs TEMPERATURE

–25 0 +25 +50 +75 +100

Temperature (°C)

Out

put S

win

g (V

)

14

13

12

11

10

R = 150L Ω

R =L ∞ Positive Swing

Negative Swing

V = ±15VS

OUTPUT SWING vs TEMPERATURE

–25 0 +25 +50 +75 +100

Temperature (°C)

Out

put S

win

g (V

)

3.1

2.9

2.7

2.5

2.3

2.1

R = 75L Ω

R =L ∞Positive Swing

Negative Swing

V = ±5VS

NONINVERTING INPUT BIAS CURRENTvs TEMPERATURE

–25 0 +25 +50 +75 +100

Temperature (°C)

+5

+4

+3

+2

+1

0

–1

–2

–3

–4

–5

V = ±5VS

V = ±15VS

I +

(µA

)B

INVERTING INPUT BIAS CURRENTvs TEMPERATURE

–25 0 +25 +50 +75 +100

Temperature (°C)

+30

+20

+10

0

–10

–20

–30

V = ±5VS

V = ±15VS

I –

(µA

)B

COMMON-MODE REJECTION vs FREQUENCY65

55

45

35

10 100 1k 10k 100k 1M 10M

Frequency (Hz)

Com

mon

-Mod

e R

ejec

tion

(dB

)

V = ±15VS

V = ±5VS

I – COMMON-MODE REJECTION RATIOB

10 100 1k 10k 100k 1M 10M

Frequency (Hz)

10

10

10

10

10

–8

–7

–6

–5

–4I –

Com

mon

-Mod

e R

ejec

tion

Rat

io (

A/V

)B

S

V = ±15VS

V = ±5V

®

OPA603 6

TYPICAL PERFORMANCE CURVES (CONT)At TA = +25°C, unless otherwise noted.

I – PSRR vs FREQUENCYB

10 100 1k 10k 100k 1M

Frequency (Hz)

10

10

10

10

10

–7

–6

–5

–4

–3I –

Pow

er S

uppl

y R

ejec

tion

Rat

io (

A/V

)B

V = ±15VS

+VS

Tracking Supplies

–VS

LARGE-SIGNALHARMONIC DISTORTION vs FREQUENCY

1

Frequency (MHz)

–30

–40

–50

–60

–70

–80

–90

–100

Har

mon

ic D

isto

rtio

n (d

Bc)

10 100

G = +2V = 2Vp-pR = 100

O

L Ω 2f

3f

V = ±15VS

10 100 1k 10k 100k 1M

Frequency (Hz)

10

10

10

10

10

–7

–6

–5

–4

–3I –

Pow

er S

uppl

y R

ejec

tion

Rat

io (

A/V

)B

V = ±5VS

+VS

Tracking Supplies

–VS

I – PSRR vs FREQUENCYB

LARGE-SIGNALHARMONIC DISTORTION vs FREQUENCY

1

Frequency (MHz)

–30

–40

–50

–60

–70

–80

–90

–100

Har

mon

ic D

isto

rtio

n (d

Bc)

10 100

G = +2V/VV = 2Vp-pR = 100

O

L Ω 2f

3f

V = ±5VS

POWER SUPPLY REJECTION vs FREQUENCY

10

Frequency (Hz)

90

80

70

60

50

40100 1k 10k 100k 1M

Tracking Supplies

–VS

+VS

Pow

er S

uppl

y R

ejec

tion

(dB

) V = ±15VS

POWER SUPPLY REJECTION vs FREQUENCY

10

Frequency (Hz)

85

75

65

55

45

35100 1k 10k 100k 1M

Tracking Supplies

Pow

er S

uppl

y R

ejec

tion

(dB

)

–VS

+VS

V = ±5VS

®

OPA6037

TYPICAL PERFORMANCE CURVES (CONT)At T

A = +25°C, unless otherwise noted.

SMALL-SIGNALHARMONIC DISTORTION vs FREQUENCY

1

Frequency (MHz)

–30

–40

–50

–60

–70

–80

–90

–100

Har

mon

ic D

isto

rtio

n (d

Bc)

10 100

G = +2V/VV = 0.5Vp-pR = 100

O

L Ω

2f

3f

V = ±15VS

SMALL-SIGNALHARMONIC DISTORTION vs FREQUENCY

1

Frequency (MHz)

–30

–40

–50

–60

–70

–80

–90

–100

Har

mon

ic D

isto

rtio

n (d

Bc)

10 100

G = +2V/VV = 0.5Vp-pR = 100

O

L Ω

2f

3f

V = ±5VS

OPEN-LOOP TRANSIMPEDANCEvs TEMPERATURE

–25 0 +25 +50 +75 +100

Temperature (°C)

500

400

300

200

V = ±5VS

V = ±15VS

Ope

n-Lo

op T

rans

impe

danc

e (k

)

Ω

2-TONE, 3rd ORDER INTERMODULATION INTERCEPT

10

Frequency (MHz)

40

30

20

10

Inte

rcep

t Poi

nt (

+dB

m)

20 30 40 50

V = ±15VS

V = ±5VS

OPEN-LOOP OUTPUT RESISTANCE vs TEMPERATURE

–25 0 +25 +50 +75 +100

125

100

75

50

25

Ope

n-Lo

op O

utpu

t Res

ista

nce

( )Ω

Temperature (°C)

V = ±15VS

V = ±5VS

MAXIMUM POWER DISSIPATION vs TEMPERATURE

–25 0 +25 +50 +75 +100

Temperature (°C)

Pow

er D

issi

patio

n (W

)2.0

1.5

1.0

0.5

Safe

®

OPA603 8

INPUT NOISE vs FREQUENCY

1

Frequency (Hz)

10

10

10

110 100 1k 10k 100k

Noi

se V

olta

ge (

nV/

Hz)

Noi

se C

urre

nt (

pA/

Hz)

10

10

10

1

Inverting Current

Noninverting Current

Voltage

3

2

3

2

V = ±15VS

INPUT NOISE vs FREQUENCY

1

Frequency (Hz)

10

10

10

110 100 1k 10k 100k

Noi

se V

olta

ge (

nV/

Hz)

Noi

se C

urre

nt (

pA/

Hz)

10

10

10

1

Inverting Current

Noninverting Current

3

2

3

2

Voltage

V = ±5VS

100

OPEN-LOOP PHASE vs FREQUENCY

Frequency (Hz)

0

–45

–90

–135

–180

Pha

se S

hift

(Deg

rees

)

V = ±15VS

V = ±5VS

1k 10k 100k 1M 10M 1G100M100

OPEN-LOOP TRANSIMPEDANCE vs FREQUENCY

1G

Frequency (Hz)

10

10

10

10

10

Tra

nsim

peda

nce

( )Ω

6

5

4

3

2

1k 10k 100k 1M 10M 100M

V = ±15VS

V = ±5VS

LARGE-SIGNAL OUTPUT vs FREQUENCY

100

Frequency (Hz)

25

20

15

10

5

0

Out

put V

olta

ge (

Vp-

p)

1k 10k 100k 1M 10M 100M

R = 150ΩL

SV = ±15V

LARGE-SIGNAL OUTPUT vs FREQUENCY

100

Frequency (Hz)

5

4

3

2

1

0

Out

put V

olta

ge (

Vp-

p)

1k 10k 100k 1M 10M 100M

R = 75ΩL

SV = ±5V

TYPICAL PERFORMANCE CURVES (CONT)At TA = +25°C, unless otherwise noted.

Noninverting Current

Voltage

Inverting Current

®

OPA6039

TYPICAL PERFORMANCE CURVES (CONT)At T

A = +25°C, unless otherwise noted.

200 IRE Full Scale

FIGURE 1. Video Differential Gain/Phase Performance.

Measured with Rohde & Schwarz Differential Gain/Phase Meter.

499Ω5pF

75Ω

75Ω

499Ω

V = ±5VS

Rohde & Schwarz SPF2Video Signal Generator Rohde & Schwarz PVF

Differential Gain/Phase MeterScopePlotter

OPEN-LOOP OUTPUT IMPEDANCE80

60

40

20

0

Ope

n- L

oop

Out

put Z

Mag

nitu

de (

)

Ω

10k 100k 1M 10M 100M

90

45

0

–45

–90

Ope

n-Lo

op O

utpu

t Z P

hase

(°)

Frequency (Hz)

V = ±15VS

OPEN-LOOP OUTPUT IMPEDANCE80

60

40

20

010k 100k 1M 10M 100M

90

45

0

–45

–90

Frequency (Hz)

V = ±5VS

Ope

n- L

oop

Out

put Z

Mag

nitu

de (

)

Ω

Ope

n-Lo

op O

utpu

t Z P

hase

(°)

0.05% Gain∆

0.0625°∆θ

®

OPA603 10

FIGURE 2. Dynamic Response, Inverting Unity-Gain.

SMALL-SIGNAL FREQUENCY RESPONSE

Frequency (Hz)

100k 1M 10M 100M

Gai

n (d

B)

+6

+3

0

–3

–6

100pF

50pF

0pF

20pF10pF

+

–VIN VO

150Ω

2.5k

V = ±15VS

2.5k

NOTE: Feedback resistor valueselected for reduced peaking.

CL =

VIN VO

150Ω CL

2.5kΩ

2.5kΩ

LARGE SIGNAL PULSE RESPONSE

Input

Output

SMALL-SIGNAL FREQUENCY RESPONSE

Frequency (Hz)

100k 1M 10M 100M

Gai

n (d

B)

+26

+23

+20

+17

+14

100pF

50pF

0pF

20pF10pF

–

+VIN

VO

3570Ω402Ω

150Ω

NOTE: Feedback resistor valueselected for reduced peaking.

V = ±15V

FIGURE 3. Dynamic Response, Gain = +10.

CL =

VIN

VO

3570Ω402Ω

150Ω CL

S

LARGE SIGNAL PULSE RESPONSE

Output

Input

With control of the open-loop characteristics of the op amp,dynamic behavior can be tailored to an application’s require-ments. Lower feedback resistance gives wider bandwidth,more frequency-response peaking and more pulse responseovershoot. The higher open-loop gain resulting from lowerfeedback network resistors also yields lower distortion.Higher feedback network resistance gives an over-dampedresponse with little or no peaking and overshoot. This maybe beneficial when driving capacitive loads. Feedback net-work impedance can also be varied to optimize dynamicperformance. To achieve wider bandwidth, use a feedbackresistor value somewhat lower than indicated in Figure 4.

EXTENDING BANDWIDTH

For gains less than approximately 20, bandwidth can beextended by adding a capacitor, C

F, in parallel with a lower

value for RF. The optimum feedback resistor value in this

case is far lower than those shown in Figure 1. For ±15Voperation, select R

F with the following equation:

APPLICATIONS INFORMATIONFor most circuit configurations, the OPA603 current-feed-back op amp can be treated like a conventional op amp. Aswith a conventional op amp, the feedback network con-nected to the inverting input controls the closed-loop gain.But with a current-feedback op amp, the impedance of thefeedback network also controls the open-loop gain andfrequency response.

Feedback resistor values can be selected to provide a nearlyconstant closed-loop bandwidth over a very wide range ofgain. This is in contrast to a conventional op amp wherecircuit bandwidth is inversely proportional to the closed-loop gain, sharply limiting bandwidth at high gain.

Figures 4a and 4b show appropriate feedback resistor valuesversus closed-loop gain for maximum bandwidth with mini-mal peaking. The dual vertical axes of these curves alsoshow the resulting bandwidth. Note that the bandwidthremains nearly constant as gain is increased.

®

OPA60311

RF (Ω) = 30 • (30 – G) for V

S = ±15V

For example, for a gain of 10, use RF = 600Ω. Optimum

values differ slightly for ±5V operation:

RF (Ω) = 30 • (23 – G) for V

S = ±5V

CF will range from 1pF to 10pF depending on the selected

gain, load, and circuit layout. Adjust CF to optimize band-

width and minimize peaking. Figure 5 shows bandwidthwhich can be acheived using this technique.

Typical values for this capacitor range from 1pF to 10pFdepending on closed-loop gain and load characteristics. Toolarge a value of CF can cause instability.

FIGURE 5. Bandwidth Results with Added Capacitor CF.

VOLTAGE GAIN vs FREQUENCY

Vol

tage

Gai

n (d

B)

30

20

10

0

–10

–201M 10M 100M 1G

Frequency (Hz)

G = 2, R = 820 , C 3pFF FΩ ≈

G = 10, R = 560 , C 3pFF FΩ ≈

G = 20, R = 220 , C 8pFF FΩ ≈

RI

RF

CF

RF

RIG = 1 +

CIRCUIT LAYOUT

With any high-speed, wide-bandwidth circuitry, careful cir-cuit layout will ensure best performance. Make short, directcircuit interconnections and avoid stray wiring capacitance—especially at the inverting input pin. A component-sideground plane will help ensure low ground impedance. Donot place the ground plane under or near the inputs andfeedback network.

Power supplies should be bypassed with good high-fre-quency capacitors positioned close to the op amp pins. Inmost cases, a 0.01µF ceramic capacitor in parallel with a2.2µF solid tantalum capacitor at each power supply pin isadequate. The OPA603 can deliver high load current—up to150mA peak. Applications with low impedance or capaci-tive loads demand large current transients from the powersupplies. It is the power supply bypass capacitors whichmust supply these current transients. Larger bypass capaci-tors such as 10µF solid tantalum capacitors may improveperformance in these applications.

POWER DISSIPATION

High output current causes increased internal power dissipa-tion in the OPA603. Copper leadframe construction maxi-mizes heat dissipation compared to conventional plasticpackages. To achieve best heat dissipation, solder the devicedirectly to the circuit board and use wide circuit boardtraces. Solder the unused pins, (1, 5 and 8) to a top-sideground plane for improved power dissipation. Limit the loadand signal conditions depending on maximum ambient tem-perature to assure operation within the power derating curve.

The OPA603 may be operated at reduced power supplyvoltage to minimize power dissipation. Detailed specifica-tions are provided for both ±15V and ±5V operation.

UNITY-GAIN OPERATION

As Figure 4b indicates, the OPA603 can be operated in unitygain. A feedback resistor (approximately 2.8kΩ) sets theappropriate open-loop characteristics and resistor R

I is omit-

ted. Just as with gains greater than one, the value of thefeedback resistor (and capacitor if used) can be optimizedfor the desired dynamic response and load characteristics.

Care should be exercised not to exceed the maximum differ-ential input voltage rating of ±6V. Large input voltage stepswhich exceed the device’s slew rate of 1000V/µs can applyexcessive differential input voltage.

FIGURE 4. Feedback Resistor Selection Curves.

BANDWIDTH AND FEEDBACK RESISTORvs INVERTING GAIN

Voltage Gain (V/V)(4a)

–1 –10 –100

Clo

sed-

Loop

Ban

dwid

th (

MH

z)

60

52.5

45

37.5

30

Fee

dbac

k R

esis

tor

(Ω)

3k

2.25k

1.5k

750

0

+

–

RF

RI

G = –RFRI

BANDWIDTH AND FEEDBACK RESISTORvs NONINVERTING GAIN

Voltage Gain (V/V)(4b)

1 10 100

Clo

sed-

Loop

Ban

dwid

th (

MH

z)

60

52.5

45

37.5

30

Fee

dbac

k R

esis

tor

(Ω)

4k

3k

2k

1k

0

+

–

RF

RI G = 1 + RFRI

®

OPA603 12

APPLICATIONS CIRCUITS

FIGURE 6. Offset Voltage Adjustment.

511Ω

261Ω

110Ω

R110Ω

C

R

5pF

f = 1

2 2 RCπ

220Ω2R

100pF

C22dB

1/2fC f C 2fC

VIN

C100pF

f = 10MHzC

VO

G = 70

OPA603

FIGURE 10. Bandpass Filter — 10MHz.

FIGURE 9. High-Pass Filter — 1MHz.

SLEWGAIN A1 R1 R2 R3 R4 –3dB RATE(V/V) OP AMP (Ω) (kΩ) (Ω) (kΩ) (MHz) (V/µs)

100 OPA627 50.5(1) 4.99 20 1 15 7001000 OPA637 49.9 4.99 12 1 11 500

This composite amplifier uses the OPA603 current-feedback op amp toprovide extended bandwidth and slew rate at high closed-loop gain.The feedback loop is closed around the composite amp, preserving theprecision input characteristics of the OPA627/637. Use separate powersupply bypass capacitors for each op amp. See Application BulletinAB-007 for details.

NOTE: (1) Minimize capacitance at this node.

NOTE: (1) Closest 1/2% value.

FIGURE 11. Precision-Input Composite Amplifier.

A1

R1

R3 R4

VI

R2

VO

(1)

OPA603

R 150for ±10VOut

L ≥ Ω

FIGURE 7. Controlling Dynamic Performance.

FIGURE 8. Low-Pass Filter — 10MHz.

VIN

511Ω

866Ω

159Ω

R

159Ω

R

C

100pF

5pF

2-pole Butterworth LPf = 10MHz

f = 1

2 RCπ

C100pF

–3dB

G = 1.6–3dB

VOOPA603

511Ω

866Ω

C1590Ω

C

R

5pF

2-pole Butterworth HPf = 1MHz

f = 1

2 RCπ

1590ΩR

100pF100pF

–3dB

G = 1.6–3dB

VIN

VOOPA603VO

RF

RG

10kΩ100kΩ

VIN+15V

–15V

OPA603

VO

1kΩ

G = 10

1kΩ

110Ω

VO

1MΩ

G = –10

1kΩ

100Ω

VB : 0V - Max Bandwidth –V - Reduced Bandwidth

MFE2000

(a)

(b)

Varying inverting input Zchanges dynamic response.

VIN

VIN

OPA603

OPA603