CHAPTER 14athena.ecs.csus.edu/.../Spring2006/EEE109/ch14_solutions.pdf14-443 CHAPTER 14 14.1 (a)...
Transcript of CHAPTER 14athena.ecs.csus.edu/.../Spring2006/EEE109/ch14_solutions.pdf14-443 CHAPTER 14 14.1 (a)...
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14-443
CHAPTER 14
14.1 (a) Common-collector Amplifier (emitter-follower)
RE
Q1
R1 R2
R3
+
-
v o
RI
v i
14.1 (b) Not a useful circuit because the signal is injected into the drain of the transistor.
R3
+
-
M1
R D
v i
RI
voR1
14.1 (c) Common-emitter Amplifier
1 k Ω
R C+
-
R3
100 k Ω
Q1
R1 R 2
RI
v i
vo
14.1 (d) Common-source Amplifier
-
14-444
+
-
R3
1 k Ω
RD
470 k Ω
M1
R2R
1v i
RI
vo
14.1 (e) Common-gate Amplifier
R1
R3RD
+
-
M1vi
RI
vo
14.1 (f) Common-collector Amplifier (emitter-follower)
R1
Q1
RER
2 R 3
+
-
vo
RI
v i
14.1 (g) Common-source Amplifier
RI
vi R
G
R 3
R D
+
-
v o
RS
J1
14.1 (h) Common-base Amplifier
-
14-445
RC
R E
Q1
R3
+
-
RI
vi
vo
-
14-446
14.1 (i) Not a useful circuit since the signal is being taken out of the base terminal.
R E
Q1
RBR3
+
-
RI
vi
vo
14.1 (j) Common-source Amplifier
1 k Ω
RD
+
-
R3
470 k Ω
M1
R2
R1
RI
vi
vo
14.1 (k) Common-gate Amplifier
R3
RD
+
-
RI
vi
voRS
M1
14.1 (l) Not a useful circuit because the signal is injected into the drain of the transistor.
R3+
-
vo
M1
R D
v i
RI
RS
-
14-447
14.1 (m) Common-source Amplifier
J 1
RG
R3
R D
+
-vi
RI
vo
14.1 (n) Common-emitter Amplifier
RB
Q1
R3
+
-
v i
RIvo
14.1 (o) Common-drain Amplifier (Source-follower)
RG
M
R 3
+
-
v i
RI
vo
14.2
vo
v i
RIRS
RGRD
CB
CC2
1k Ω
RL
100 k Ω-VSS
VDD
CC1
+
-
-
14-448
14.3
RI
v i
RS
CC1
CC2
RG
RD
CB
VDD
-V SS
RL1kΩ
100 k Ω
vo
+
-
14.4
RI
v i
RS
-VSS
RG
RD
CB
RL
100 k Ω
CC1
CC2
VDD
1k Ω
vo
+
-
14.5
+15 V
220 kΩ
15 kΩ
-15 V
150 kΩ
22 kΩ
+
-
vO
v I
RI
3.3 k Ω
RE
RB
RC
RLCC1
CC2
CB
Q1
-
14-449
14.6
(a)
+15 V
220 k Ω
15 kΩ
-15 V150 kΩ22 k Ω
+
-
vO
v I
RI
3.3 k Ω
RE
RB
RC
RL
CC1
CC2
CB
Q1
(b)
+15 V
220 kΩ
-15 V150 kΩ22 kΩ
+
-
vO
v I
RI
3.3 k Ω
RE
RB
RL
CC1
CC2
Q1
14.7
(a)
+15 V
220 kΩ
15 kΩ
-15 V
3.3 k Ω
150 kΩ
22 kΩ
+
-
vO
RE
RB
RC
RL
CC1
CC2
CB
vI
RI
Q1
(b)
+15 V
15 kΩ
-15 V
3.3 kΩ
150 k Ω
22 kΩ
+
-
vO
RE
RC
RL
CC1
CC2
v I
RI
Q1
14.8
a( ) Neglecting Rout : Avt = −gmRL
1+ gmRS= −
0.005S( ) 2000Ω( )1+ 0.005S( ) 200Ω( )
= −5.00
Av = AvtRG
RI + RG= -5
1MΩ75kΩ+ 1MΩ
= -4.65 | Rin = RG = 1MΩ
Rout = ro 1+ gmRS( )=10kΩ 1+ 0.005S( ) 200Ω( )[ ]= 20.0 kΩ >> 2kΩ
Ai = −RGgm
1+ gmRS= −1MΩ
0.005S1+ 0.005S( ) 200Ω( )
= −2500
b( ) Av = −gm RL ro( ) RGRI + RG
= − 0.005S( ) 2kΩ 10kΩ( ) 1MΩ
75kΩ + 1MΩ
= −7.75
Rin = RG = 1MΩ | Rout = ro = 10.0 kΩ | Ai = −RGgm = −1MΩ 0.005S( )= −5000
-
14-450
14.9
a( ) gm = 0.02S | rπ =75.02
= 3750Ω
Rin = RB rπ + βo + 1( )RE[ ]=15kΩ 3750Ω + 76 200Ω( )[ ]= 8.37 kΩ
Neglecting Rout : Av = AvtRin
RI + Rin
= −
βoRLrπ + βo +1( )RE
RinRI + Rin
Av = −75 12kΩ( )
3750Ω + 76 200Ω( )8.37kΩ
500Ω+ 8.37 kΩ
= −44.8
Rout ≅ ro 1+βoRE
Rth + rπ + RE
= 100kΩ 1+
75 200Ω( )15kΩ 500Ω( )+ 3750Ω+ 200Ω
= 438 kΩ >> 12kΩ
Ai = −βoRB
RB + rπ + βo +1( )RE= −75
15kΩ15kΩ + 3750Ω + 76 200Ω( )
= −33.1
a( ) gm = 0.02S | rπ =75.02
= 3750Ω
Rin = RB rπ + βo +1( )RE[ ]= 15kΩ 3750Ω+ 76 560Ω( )[ ]= 11.3 kΩ
Neglecting Rout : Av = AvtRin
RI + Rin
= −
βoRLrπ + βo +1( )RE
RinRI + Rin
Av = −75 12kΩ( )
3750Ω + 76 560Ω( )11.3kΩ
500Ω+ 11.3kΩ
= −18.6
Rout ≅ ro 1+βoRE
Rth + rπ + RE
= 100kΩ 1+
75 560Ω( )15kΩ 500Ω( )+ 3750Ω + 560Ω
= 976 kΩ >>12kΩ
Ai = −βoRB
RB + rπ + βo +1( )RE= −75
15kΩ15kΩ + 3750Ω + 76 560Ω( )
= −18.3
14.10
a( ) For large βo : Av ≅ −RLRE
= −8.2kΩ 47kΩ330Ω + 680Ω
= −6.91 | b( ) Place a bypass capacitor in
parallel with the 330 Ω resistor. Then Av ≅ −RLRE
= −8.2kΩ 47kΩ
680Ω= −10.3 | c( ) Place a
bypass capacitor in parallel with the 680 Ω resistor. Then Av ≅ −8.2kΩ 47kΩ
330Ω= −21.2
d( ) Place a bypass capacitor from the emitter to ground. e( ) Av ≅ −10 VCC + VEE( )= −240.
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14-451
14.11 Rin = rπ + βo + 1( )RE = 500 kΩ
Avt = −βoRL
rπ + βo + 1( )RE= −
75RL500kΩ
= −10 → RL = 66.7 kΩ
Assuming βo +1( )RE >> rπ , RE ≅500 kΩβo + 1
=500 kΩ
76= 6.58 kΩ
Note : The nearest 5% values would be 68 kΩ and 6.8 kΩ.
14.12
Rin = rπ = 500 kΩ | rπ =βogm
=βoVT
IC | IC =
βoVTrπ
=75 0.025V( )
500kΩ= 3.75 µA
Av = −gmRLrπ
Rth + rπ
= −
βoRLRth + rπ
= −75RL
100Ω + 500kΩ= −10 | RL = 66.7 kΩ
Closest 5% value is RL = 68kΩ.
14.13
R thR5
ro
vd
i x
vgs
gm vgs
+ -
ix − gmvgs+gmvgs
=
go −go−go go + GS
vdvs
| vgs = −vs
ix0
=
go − gm + go( )−go gm + go + GS
vdvs
∆ = goGS | vd = gm + go + GS( )ix∆
=gm + go + GS( )
goGSix
Rout =vdix
= RS 1+gmgo
+GSgo
= RS 1+ µf +
roRS
Rout = ro + 1+ µ f( )RS ≅ ro + µ f RS = ro 1+ gmRS( )
14.14
ix + gm' ve
−gm' ve
=
go −go−go go + GE + G1
vxve
|
ix0
=
go − gm' + go( )
−go gm' + go + GE + G1
vxve
∆ = go GE +G1( ) | vx = gm' + go + GE + G1( )ix∆ =gm
' + go + GE +G1( )( )go GE +G1( )
ix
Rout =vxix
= RE R1( )1+ gm'
go+
GE + G1go
= RE R1( )1+ gm' ro + roRE R1( )
Rout = RE R1( )+ ro + ro gmrπRth + rπRE Rth + rπ( )Rth + rπ + RE
= RE R1( )+ ro 1+ βoRERth + rπ + RE
-
14-452
14.15 From the results in Table 14.1,
AvtCE = −
gmRL1+ gmRE
= −RL
1gm
+ RE= −
RLre + RE
for re =1gm
AvtCS = −
gmRL1+ gmRS
= −RL
1gm
+ RS= −
RLre + RS
for re =1gm
14.16
VEQ =1262kΩ
20kΩ+ 62kΩ= 9.07V | REQ = 20kΩ 62kΩ = 15.1kΩ
IB =12 − 0.7 − 9.07( )V
15.1kΩ + 75 + 1( )3.9kΩ= 7.16µA | IC = 537 µA | VEC = 12− 3900IE − 8200IC = 5.47 V
Active region is correct. | rπ =75 0.025V( )
537µA= 3.49kΩ | VA not specified, choose ro = ∞
Rin = 15.1kΩ 3.49kΩ = 2.83 kΩ | Rout = ro 8.2kΩ = 8.2 kΩ | gm = 40IC = 21.5 mS
RL = ro 8.2kΩ 100kΩ = 8.2kΩ 100kΩ = 7.58kΩ
Av = −gmRLRin
RI + Rin
= − 21.5mS( ) 7.58kΩ( ) 2.83kΩ
1kΩ+ 2.83kΩ
= −120
Ai =RB
RB + rπ−βo( )
RoutRout + R3
=15.1kΩ
15.1kΩ + 3.49kΩ−75( ) 8.2kΩ
8.2kΩ + 100kΩ= −4.62
vbe = v iRin
RI + Rin= v i
2.83kΩ1kΩ + 2.83kΩ
= 0.739v i | v i =5.00mV0.739
= 6.76 mV
Av ≅ −10VCC = −10 12( )= −120. | The voltage gain is identical to the rule - of - thumb estimate.
14.17
VEQ =18500kΩ
1.4MΩ+ 500kΩ= 4.74V | REQ = 500kΩ 1.4MΩ = 368kΩ
4.74 = VGS + 27000ID = 1+2IDS
250x10−6+ 27000ID → ID =104µA
VDS =18 − ID 75kΩ+ 27kΩ( )= 7.39V | Active region operation is correct.
gm = 2 250x10−6( )104x10−6( )= 0.228mS | Assume λ = 0, ro = ∞.
RL = ro 75kΩ 470kΩ ≅75kΩ 470kΩ = 64.7kΩ
Rin = RG = R1 R2 = 368 kΩ | Rout = ro 75kΩ ≅ 75kΩ
-
14-453
Av = −gmRLRin
RI + Rin= − 0.228mS( ) 64.7kΩ( ) 368kΩ
1kΩ + 368kΩ
= −14.7
Ai = RG −gm( )RD
RD + R3= 368kΩ −0.228mS( ) 75kΩ
75kΩ + 470 kΩ= −11.5
vgs = viRin
RI + Rin= v i
368 kΩ1kΩ + 368kΩ
= 0.997v i | VGS −VTN =2 104µA( )
250µA /V 2= 0.912V
vgs ≤ 0.2 VGS −VTN( )→ vi ≤ 0.20.912V0.997
= 0.183 V | Av ≅ −VDD
VGS −VTN= −
180.912
= −19.7
The rule - of - thumb estimate assumes VRL =VDD
2. We have VRL =104µA 75kΩ( )= 7.80V = 0.433VDD
The estimate also doesn' t account for the presence of R 3 .
14.18
VEQ =182.2MΩ
2.2MΩ + 2.2MΩ= 9.00V | RG = REQ = 2.2MΩ 2.2MΩ = 1.10MΩ
18 = 22000ID − VGS + 9 | 9 = 22000ID + 1+2ID
400x10−6→ ID = 307µA
VDS = − 18 − ID 22kΩ +18kΩ( )[ ]= −5.72V | Active region operation is correct.gm = 2 400x10
−6( ) 307x10−6( )= 0.496mS | Assume λ = 0, ro = ∞RL = ro 18kΩ 470kΩ ≅18kΩ 470kΩ = 17.3kΩ | Rin =1.10 MΩ | Rout = ro 18kΩ = 18kΩ
Av = −gmRLRin
RI + Rin
= − 0.496mS( )17.3kΩ( ) 1.1MΩ
1kΩ + 1.1MΩ= −8.57
Ai = −gmRinRD
RD + R3= −0.496mS 1.1MΩ( ) 18kΩ
18kΩ+ 470kΩ= −18.3
vgs = v iRin
RI + Rin= v i
1.1MΩ1kΩ +1.1MΩ
= 0.999v i | VGS −VTN =2 307µA( )400µA /V 2
=1.24V
vgs ≤ 0.2 VGS − VTN( ) | v i ≤ 0.21.24V0.999
= 0.248 V
14.19
VGS = − 11kΩ( )ID = − 11kΩ( ) 20mA( ) 1−VGS−4
2
→ VGS = −3.50V , ID = −VGS
11kΩ= 318 µA
VDS = 20− ID 11kΩ + 39kΩ( )= 4.10V | Active region operation is correct.
gm =2−4
20mA 318µA( ) = 1.26mS | Assume λ = 0, ro = ∞. | RL = 39kΩ 500kΩ = 36.2kΩ
Rin = RG =1.00 MΩ | Rout = 39kΩ
-
14-454
Av = −gmRL
1+ gmRS
RinRI + Rin
= −
1.26mS 36.2kΩ( )1+ 1.26mS 11kΩ( )
1MΩ500Ω+ 1MΩ
= −3.07
Ai = −RGgm
1+ gmRS
RDRD + R3
= −106
1.26mS1+1.26mS 11kΩ( )
39kΩ39kΩ + 500kΩ
= −6.14
vgs =Rin
RI + Rinv i =1.00v i | VGS −VP = −3.5− −4( ) = 0.500V
vgs ≤ 0.2 VGS − VP( ) 1+gmRS( ) | v i ≤ 0.2 0.5( )1+ 1.26mS 11kΩ( )[ ]=1.49 V
14.20 VGS = 0 → ID = IDSS = 5.00mA | VDS = 16 −1800ID = 7.00V | Active region operation is correct.
gm =2
−55mA 5mA( ) = 2.00mS | Assume λ = 0, ro = ∞.
Av = -gmRLRG
RI + RG
= − 2.00mS( ) 1.8kΩ 36kΩ( ) 10MΩ
10MΩ +5kΩ
= −3.43
Rin = 10.0 MΩ | Rout = RD ro =1.80 kΩ
Ai = −gmRGRD
RD + R3
= −2.00mS 10MΩ( ) 1.8kΩ
1.8kΩ+ 36kΩ
= −952
vgs = v i10MΩ
10MΩ +5kΩ
≤ 0.2VGS − VP → v i ≤ 1 V
14.21
IB =10 − 0.7( )V
20kΩ+ 80+ 1( )9.1kΩ=12.3µA | IC = 983 µA | VCE = 20− 9100IE =11.0 V
Active region is correct. | rπ =80 0.025V( )
983µA= 2.04kΩ | ro =
100 + 11.0( )V983µA
= 113kΩ
RL = ro 1MΩ =113kΩ 1MΩ = 102kΩ | Rin = RB rπ = 20kΩ 2.04kΩ = 1.85 kΩ | Rout = ro =113 kΩ
Av = -gmRLRin
RI + Rin
= −40 983µA( )102kΩ( ) 1.85kΩ
250Ω + 1.85kΩ= −3530
Ai = −βoRB
RB + rπ
roro + R3
= −80
20kΩ20kΩ + 2.04kΩ
113kΩ113kΩ +1MΩ
= −7.37
vbe = v iRin
RI + Rin
= v i
20kΩ250Ω + 20kΩ
= 0.988v i | v i ≤5.00mV0.988
= 5.06 mV
14.22 From Table 14.3,
AvtCC ≅ Avt
CD =gmRL
1+ gmRL=
RL1
gm+ RL
=RL
re + RL for re =
1gm
-
14-455
14.23
rπ =80
0.4S= 200Ω | Assume VA = ∞, ro = ∞.
Rin = RB rπ + βo +1( )RL[ ]= 47kΩ 200Ω + 811kΩ( )[ ]= 29.8 kΩ
Rout =Rth + rπβo + 1
=47kΩ 10kΩ( )+ 200Ω
81=104 Ω
Av = +βo + 1( )RL
rπ + βo + 1( )RLRin
RI + Rin
=
811kΩ( )200Ω + 81 1kΩ( )
29.8kΩ10kΩ + 29.8kΩ
= 0.747
Ai = + βo + 1( )RB
RB + rπ + βo + 1( )RL
roro + RL
= 81
47kΩ47kΩ + 200Ω + 811kΩ( )
= 29.7
14.24
Assume λ = 0, ro = ∞. | Rin = RG = 2 MΩ | Rout =1gm
= 100 Ω
Av = +gmRL
1+ gmRL
RinRI + Rin
=
0.01 1kΩ( )1+ 0.01 1kΩ( )
2MΩ100kΩ+ 2MΩ
= 0.866
Ai = +gmRGro
ro + RL
= 0.01 2MΩ( )= 2x104
14.25 Defining v1 as the source node:
a( ) 2kΩ 100kΩ = 1.96kΩv i − v1( )106
+ 3.54 x10−3 v i − v1( )=v1
19603.541x10−3v i = 4.051x10
−3v1v1 = 0.874v i | Av = 0.874
Rin =v iii
=v i
10−6 v i − v1( )= 7.94 MΩ
Driving the output with current source ix :
Rout : ix =v1
106+
v12000
+ 3.54 x10−3v1
Rout =v1ix
= 247 Ω | b( ) Rin = ∞
g mvgs
2 k Ω 100 k Ω
vgs
+
-+
-
1 M Ω
v1v i
RG
-
14-456
14.26
IB =5 − 0.7( )V
1MΩ + 100 + 1( )430kΩ= 96.8nA | IC = 9.68µA | VCE =10 − 430000IE = 5.80V
Active region is correct. | rπ =100 0.025V( )
9.68µA= 258kΩ | ro =
60 + 5.80( )V9.68µA
= 6.80MΩ - neglected
In the ac model, R1 appears in parallel with rπ . The circuit appears to be using a transistor with
rπ' = 500kΩ rπ =170kΩ and βo
' = gmrπ' = 40 9.68µA( )170kΩ = 65.8
RL = 500kΩ 430kΩ 500kΩ = 158kΩ | Rin = rπ' + βo
' +1( )RL = 170kΩ + 66.8 158kΩ( )= 10.7 MΩ
Av =βo
' + 1( )RLrπ
' + βo' + 1( )RL
RinRI + Rin
=
66.8 158kΩ( )170kΩ + 66.8 158kΩ( )
10.7MΩ500Ω+ 10.7MΩ
= +0.984
Rout = RE R2RI + rπ
'
βo' +1
= 430kΩ 500kΩ500Ω +170kΩ
66.8= 2.52 kΩ
vbe = v irπ
'
RI + rπ' + βo
' + 1( )RL= v i
170kΩ500Ω+ 170kΩ+ 66.8 158kΩ( )
= 1.58x10−2v i
v i ≤0.005V
1.58x10−2= 0.315 V
14.27
VEQ =1851kΩ
51kΩ + 100kΩ= 6.08V | REQ = 51kΩ 100kΩ = 33.8kΩ
IB =6.08 − 0.7 + 18( )V
33.8kΩ + 126( ) 4.7kΩ( )= 37.3µA | IC = 4.67 mA | VCE = 36 − 2000IC − 4700IE = 4.54 V
Active region is correct. | rπ =125 0.025V( )
4.67mA= 669Ω | ro =
50 + 4.54( )V4.67mA
= 11.7kΩ
RB = R1 R2 = 51kΩ 100kΩ = 33.8kΩ | RL = R3 RE ro = 24kΩ 4.7kΩ 11.7kΩ = 2.94kΩ
Rin = RB rπ + βo +1( )RL[ ]= 33.8kΩ 669Ω + 126( )2.94kΩ[ ]= 31.0 kΩ
Av = +βo + 1( )RL
rπ + βo + 1( )RLRin
RI + Rin
=
126 2.94kΩ( )0.669kΩ + 126 2.94kΩ( )
31.0kΩ500Ω + 31.0 kΩ
= 0.982
vbe = v iRin
RI + Rin
rπrπ + βo +1( )RL
=
31.0kΩ500Ω+ 31.0 kΩ
0.669kΩ0.669kΩ+ 126 2.94kΩ( )
= 1.77x103v i
v i ≤0.005V
1.77x10−3= 2.82 V | Rout = RE
RB RI( )+ rπβo +1
= 4.7kΩ33.8kΩ 500Ω( )+ 669Ω
126= 9.22 Ω
-
14-457
14.28
VGS = 5V | ID =4x10−4
25−1( )2 = 3.2mA | VDS = 5 − −5( )=10V - Pinchoff region
operation is correct. | gm = 2 4x10−4( ) 3.2mA( )1+ 0.02 10( )[ ]= 1.75mS
ro =
10.02
+ 10
3.2VmA
=18.8kΩ − Cannot neglect! | RL =18.8kΩ 100kΩ =15.8kΩ
Rin = RG = 1 MΩ | Rout =1gm
ro = 555 Ω
Av = +Rin
RI + Rin
gmRL1+ gmRL
= +
1MΩ10kΩ + 1MΩ
1.75mS 15.8kΩ( )1+1.75mS 15.8kΩ( )
= 0.956
vgs = v iRin
RI + Rin
11+ gmRL
= v i
106Ω104 Ω+ 106Ω
11+1.75mS 15.8kΩ( )
= 0.0346v i
v i ≤0.2 5 −1( )0.0346
= 23.2 V But, vDS must exceed vGS − VTN ≅ VGS −VTN = 4V for pinchoff.
VDS =10 − vo =10 − 0.956v i ≥ 4 → v i ≤ 6.28 V − Limited by the Q - point voltages
14.29 βo = gmrπ = 3.54 mS 1MΩ( )= 3540 | RL = 2kΩ 100kΩ = 1.96kΩ
Av =βo + 1( )RL
rπ + βo + 1( )RL=
3540 + 1( ) 1.96kΩ( )1MΩ + 3540 +1( )1.96kΩ( )
= 0.874
Rin = rπ + βo + 1( )RL = 1MΩ + 3540 + 1( ) 1.96kΩ( )= 7.94 MΩ
Rout = 2kΩrπ
βo + 1( )= 2kΩ
106
3541( )= 247 Ω
14.30 v i ≤ 0.005 1+ gmRL( ) | RL = RE R7 ≅ RE
v i ≤ 0.005 1+ gmRL( )= 0.005 1+ gmRE( ) = 0.005 1+IC REVT
v i ≤ 0.005 1+ αFIEREVT
≅ 0.005 1+
IEREVT
v i ≤ 0.005 1+VREVT
= 0.005 1+
VRE0.025
= 0.005+ 0.2VRE
-
14-458
14.31
a( ) vbe = v i − vo | 0.005 ≤ 5 − vo → Av =vov i
≥4.995
5= 0.999
b( ) Av =βo + 1( )RE
rπ + βo + 1( )RE=
1
1 + rπβo +1( )RE
=1
1+ βoβo +1( )
rπβoRE
=1
1+ αogmRE
=1
1+ VTIERE
1
1+ VTIERE
≥ 0.999 →VT
IERE≤ 0.001 → IE RE ≥
0.025V0.001
= 25.0 V
14.32
vbe = v i − vo = 1− Av( )v i | 0.005 ≤ 1− Av( )7.5 → Av =vov i
≥7.5 − 0.005
7.5= 0.999333
From Prob. 14.30, Av =1
1+VT
IERL
| RL = RE 500Ω =500RE
500+ RE | Av =
1
1+VT
IERE
500+ RE500
1
1+VT
IERE
500+ RE500
≥ 0.999333→VT
IERE
500+ RE500
≤ 6.67x10−4
500IE RE500 + RE
≥0.025V
6.67x10−4= 37.5V | VCC ≥ IERE +0.7 +7.5
Some design possibilities are listed in the table below.
RE IE VCC VCC IE
100 Ω 450 mA 53 V 24 W
250 Ω 225 mA 64 V 16 W
360 Ω 179mA 73V 13 W
500 Ω 150 mA 83 V 12 W
750 Ω 125 mA 102 V 13 W
1000 Ω 113mA 120 V 14 W
2000 Ω 93.8 mA 196 V 18 W
Using a result near the minimum-power case in the table: RE = 510 Ω? ?? E?= 149 mA and VCC = 85 V.
Assuming βF = 50 : IB ≅149mA
51= 2.92 mA | Set IR1 = 5IB = 14.6mA ≅ 15mA
R1 =VE + VBE
IR1=
149mA 510Ω( )+ 0.715mA
= 5.07kΩ → 5.1 kΩ | IR2 = IR1 + IB ≅18mA
R2 =85 −VBE − VBE
IR2=
8.3V18mA
= 462Ω → 470 Ω
It is very difficult to achieve the required level of linearity!
-
14-459
14.33
a( ) Rin = R41gm
= 3kΩ1
0.5mS=1.20 kΩ | Rout = ∞ (assume λ = 0)
Av =gmRL
1+ gm RI R4( )R4
RI + R4
=
0.5mS 100kΩ( )1+ 0.5mS 50Ω 3kΩ( )
3kΩ50Ω + 3kΩ
= 48.0
Ai = 1R4
R4 +1gm
=3kΩ
3kΩ+ 2kΩ= 0.600
b( ) Av =0.5mS 100kΩ( )
1+ 0.5mS 5kΩ 3kΩ( )3kΩ
5kΩ + 3kΩ
= 9.68 | Rin = 5kΩ
10.5mS
= 1.43 kΩ
Rout = ∞ | Ai =5kΩ
5kΩ + 2kΩ= 0.714
14.34
a( ) rπ =100 0.025V( )
12.5µA= 200kΩ | gm = 40 12.5µA( )= 0.5mS
Rin = R4rπ
βo + 1= 100kΩ
200kΩ101
= 1.94 kΩ
Av =gmRL
1+ gm RI R4( )R4
RI + R4
=
0.5mS 100kΩ( )1+ 0.5mS 50Ω 100kΩ( )
100kΩ50Ω +100kΩ
= 48.7
Rout = ro 1+gm RI R4( )[ ]= 60V12.5µA 1+ 0.5mS 50Ω( )[ ]= 4.92 MΩ
Ai = αoR4
RI + R4
= 0.990
100kΩ50Ω +100kΩ
= 0.990
b( ) Av =0.5mS 100kΩ( )
1+ 0.5mS 2.2kΩ 100kΩ( )100kΩ
2.2kΩ +100kΩ
= 23.6 | Rin = 1.94kΩ - no change
Rout = ro 1+gm RI R4( )[ ]= 60V12.5µA 1+ 0.5mS 2.2Ω( )[ ]=10.1 MΩ
14.35 The voltage gain is approximately 0. The signal is injected into the collector and taken out of the emitter. This is not a useful amplifier circuit.
14.36 For R4 >> RI in Table 14.5,
AvtCB = Avt
CG = +gmRL
1+ gmRth= +
RL1
gm+ Rth
= +RL
re + Rth for re =
1gm
-
14-460
14.37
ID =2x10−4( )
2VGS + 1( )
2 | 15 + VGS
68kΩ= 10−4 VGS + 1( )
2 → VGS = −2.363V
ID =15 + VGS
68kΩ = 186µA | VDS = − 30 − 68kΩ+ 43kΩ( )ID[ ]= −9.35V |
Pinchoff region is correct. | gm =2 186µA( )2.36 −1
= 0.274mS | Rin = 68kΩ1
gm= 3.46kΩ
Rout = RD = 43kΩ | RL = 43kΩ 200kΩ = 35.4kΩ
Av =Rin
RI + RingmRL =
3.46kΩ0.250kΩ + 3.46kΩ
0.274mS( ) 35.4kΩ( )= 9.05
Ai = AvRI + Rin
R3= 9.05
3.71kΩ200kΩ
= 0.168 | vgs = v i
3.46kΩ0.250kΩ+ 3.46kΩ
≤ 0.2 VSG −1( )
v i3.46kΩ
0.250kΩ + 3.46kΩ≤ 0.2 2.36 −1( )→ v i ≤ 0.292 V
14.38
VGS = −12+ 33kΩ( )ID | VGS = −12 +3.3x104( )2x10−4( )
2VGS + 1( )
2
VGS = −2.68V & ID =2x10−4( )
2VGS + 1( )
2 = 282µA
VDS = − 24 − ID 33kΩ + 24kΩ( )[ ]= −7.93 V - Active region operation is correct.gm = 2 2x10
−4( ) 2.82x10−4( )= 3.36x10−4 S | R I RS = 0.5kΩ 33kΩ = 493ΩAssume λ = 0, ro = ∞ | RL = RD R3 = 24kΩ 100kΩ = 19.4kΩ
Av =gmRL
1+ gm RI RS( )RS
RI + RS
=
0.336mS 19.4kΩ( )1+ 0.336mS 493Ω( )
33kΩ500Ω+ 33kΩ
= 5.51
Ai = 1RS
RS +1gm
RDRD + R3
=
33kΩ33kΩ + 2.98kΩ
24kΩ24kΩ+ 100kΩ
= 0.178
Rin = RS1gm
= 2.73 kΩ | Rout = RD = 24kΩ
vgs = viRIN
RI + RIN≤ 0.2VGS +1 | v i
2.73kΩ0.5kΩ + 2.73kΩ
≤ 0.2 1.68( )→ vs ≤ 0.398 V
-
14-461
14.39
IB =9− 0.7( )V
100kΩ + 50 +1( )82kΩ=1.94µA | IC = 96.9 µA
VCE =18 − 82000IE − 39000IC = 6.12 V | Active region operation is correct.
gm = 40IC = 3.88mS | rπ =βogm
= 12.9kΩ | ro =50 + 6.12( )V
96.9µA= 579kΩ - neglected
RI RE = 0.5kΩ 82kΩ = 497Ω | RL = RC R3 = 39kΩ 100kΩ = 28.1kΩ
Av =gmRL
1+ gm RI RE( )RE
RI + RE
=
3.88mS 28.1kΩ( )1+ 3.88mS 497Ω( )
82kΩ500Ω+ 82kΩ
= 37.0
Rin = 82kΩrπ
βo +1= 252Ω | Ai = Av
RI + RinR3
= 37.0500Ω+ 252Ω
100kΩ= 0.278
Rout = RC = 39.0 kΩ | veb = v iRin
RI + Rin≤ 5.00mV | 0.335v i ≤ 5.00mV | v i ≤ 14.9 mV
14.40
IB =9− 0.7( )V
1000kΩ + 50 +1( )820kΩ=194nA | IC = 9.69 µA
VCE =18 − 820000IE − 390000IC = 6.12 V | Active region is correct.
gm = 40IC = 0.388mS | rπ =βogm
=129kΩ | ro =50+ 6.12( )V
9.69µA= 5.79MΩ - neglected
RI RE = 5kΩ 820kΩ = 4.97kΩ | RL = RC R3 = 390kΩ 1MΩ = 281kΩ
Av =gmRL
1+ gm RI RE( )RE
RI + RE
=
0.388mS 281kΩ( )1+ 0.388mS 4.97kΩ( )
820kΩ5kΩ+ 820kΩ
= 37.0
Rin = 820kΩrπ
βo +1= 2.52 kΩ | Ai = Av
RI + RinR3
= 37.05kΩ + 2.52kΩ
1MΩ= 0.278
Rout = RC = 390 kΩ | veb = v iRin
RI + Rin≤ 5.00mV | 0.335v i ≤ 5.00mV | v i ≤ 14.9 mV
14.41
VGS = −3900ID = −39005x10−4( )
2VGS + 2( )
2 | VGS = −0.975 VGS + 2( )2 → VGS = −0.9915V
ID =5x10−4( )
2VGS + 2( )
2 = 254µA | VDS =15 − 23.9kΩID = 8.92V - Pinched off.
-
14-462
gm =2 254µA( )2 − 0.992
= 0.504mS | Rin = 3.9kΩ1gm
= 1.32kΩ | Rout = RD = 20kΩ
RL = 20kΩ 51kΩ =14.4kΩ
Av =gmRL
1+ gm RI RS( )RS
RI + RS
=
0.504mS 14.4kΩ( )1+ 0.504mS 0.796kΩ( )
3.9kΩ1kΩ+ 3.9kΩ
= 4.12
Ai = AvRI + Rin
R3= 4.121kΩ+ 1.32kΩ
51kΩ= 0.187
vgs = v i1.32kΩ
1kΩ + 1.32kΩ≤ 0.2 VGS + 2( ) | v i
1.32kΩ1kΩ +1.32kΩ
≤ 0.2 −0.992 + 2( )→ v i ≤ 0.354 V
14.42
For R th >1gm
, Av ≅RLRth
For large R th, all of the Thevenin equivalent source
current, v thRth
, goes into the transistor source terminal.
14.43
Rin =rπ + 1.5kΩ
βo +1 | rπ =
75 0.025V( )1mA
= 1.88kΩ | Rin =1.88kΩ + 1.5kΩ
76= 44.5 Ω
14.44
gm =2−2
1mA 5mA( ) = 2.24mS | Rin =1gm
= 447 Ω
14.45
gm = 2 1.25mA( ) 1mA( ) = 1.58mS | Rin =1gm
= 633 Ω
14.46
a( ) Rout = ro 1+βoRE
rπ + RE
| IE =
15V − 0.7V143kΩ
= 100µA | For βF =100, IC = 99.0µA
rπ =100 0.025V( )
99.0µA= 25.3kΩ | ro ≅
50V99.0µA
= 505kΩ
Rout = 505kΩ 1+100 143kΩ( )
25.3kΩ + 143kΩ
= 43.4 MΩ b( ) 0 V
-
14-463
c( ) IE =15V − 0.7V
15kΩ= 953µA | For βF =100, IC = 944µA | rπ =
100 0.025V( )944µA
= 2.65kΩ
ro ≅50V
944µA= 53.0kΩ | Rout = 53.0kΩ 1+
100 15kΩ( )15kΩ + 2.65kΩ
= 4.56 MΩ | VCB ≥ 0 V
14.47
Rout = βo + 1( )ro = βo +1( )VA + VCE
IC
= 126
50 +10.749.6µA
= 154 MΩ
14.48
Rin = 0.5MΩ | Av =104620 = 200 | Fairly large Rin, large gain
A common - emitter amplifier operating at a low current can achieve both alarge gain and input resistance. Av ≅ 20VCC → VCC = 10VAchieving this gain with an FET is much more difficult :
Av ≅VDD
VGS −V TN=
VDD0.25V
→ VDD ≅ 50V which is unreasonably large.
14.49
Rin = 10MΩ | Av = 102620 = 20 | Large Rin, moderate gain
These requirements are readily met by a common - source amplifier.
For example, Av ≅VDD
VGS −V TN=
15V0.5V
= 30.
A common - emitter stage operating at a low collector current with
an unbypassed emitter resistor RE ≅10MΩ
100=100kΩ
is a second possibility,
but the circuit will require careful design.
14.50 An inverting amplifier with a gain of 40 dB is most easily achieved with a common - emitterstage : Av ≅ 10VCC → VCC =10 V . The input resistance can be achieved by shunting the
input with a 5 - Ω resistor. Setting rπ = 5 Ω would require IC ≅100 0.025V( )
5Ω= 0.5A and would
waste a large amount of power to achieve the required input resistance.
14.51 0 - dB gain corresponds to a follower ( Av = 1).
For an emitter - follower, R in ≅ βo + 1( )RL ≅101 20kΩ( )= 2.02 MΩ. So an BJTcannot meet the input resistance requirement. A source follower provides a gain of approximately 1 and can easily achieve the required input resistance.
14.52
-
14-464
A non - inverting amplifier with a gain of 20 and an input resistance of 5 k Ω shouldbe readily achievable with either a common - base or common - gate amplifier with proper choice of operating point. The gain of 10 is easily achieved with either the
FET or BJT design estimate : Av ≅VDD
VGS − VTN or Av ≅ 10VCC . Rin ≅
1gm
= 5 kΩ is within
easy reach of either device. The gain and input resistance can also be easily metwith either a common - emitter, or common - source stage with a resistor shunt at the input.
14.53
A gain of 0.97 and an input resistance of 400k Ω should be achievable with
either a source - follower or emitter - follower. For the FET, Av ≅gmRL
1+ gmRL= 0.97
requires gmRL = 33.3 : 2IDRL
VGS − VTN= 33.3 → IDRL = 8.3V for a design with VGS − VTN = 0.5V .
The BJT can achieve the required gain with a much lower power supply and
can still meet the Rin requirement : Rin ≅ βoRL ≅100 5kΩ( )= 500kΩ.
Av ≅gmRL
1+ gmRL= 0.97 | gmRL = 33.3→ IC RE = 33.3 0.025( )= 0.833 V .
The requirements can be met with careful bias circuit design and specificationof a BJT with minimum current gain of at least 100.
14.54
Av = 106620 = 2,000. This value of voltage gain approaches the amplification factor
of the BJTs : Av ≤ µ f = 40VA = 40 75( )= 3000. Such a large gainrequirement cannot be met with single - transistor BJT amplifiers using theresistive loaded amplifiers in this chapter (Remember the 10 - VCC limit). FETstypically have much lower values of µf and are at an even worse disadvantage.None of the single - transistor amplifier configurations can meet the gain requirements.
14.55
Rout =Rth + rπβo + 1
| Assuming Rth ≅ RI and rπ = 0, Rout ≥RI
βo +1=
250151
=1.66Ω
-
14-465
14.56 Rin = rπ + βo + 1( )RE ≅ rπ + βoRE = rπ 1+ gmRE( ) | rπ' = rπ 1+ gmRE( )
gm' =
icv i
=βo
rπ + βo +1( )RE≅
βorπ + βoRE
=βo
rπ 1+ gmRE( )=
gm1+ gmRE
ro' =
icvc v i =0
= ro 1+βoRE
rπ + RE
≅ ro 1+
βoRErπ
= ro 1+ gmRE( ) for rπ >> RE
βo' = gm
' rπ' =
gm1+ gmRE
rπ 1+ gmRE( )= βo | µ f' = gm' ro' =
gm1+ gmRE
ro 1+ gmRE( )= µ f
14.57 *Problem 14.57 - Common-Emitter Amplifier 5mV VCC 6 0 DC 9 VEE 4 0 DC -9 VS 1 0 SIN(0 0.005 1K) C1 1 2 1U RB 2 0 10K RC 6 5 3.6K RE 3 4 2K C2 3 0 50U C3 5 7 1U R3 7 0 10K Q1 5 2 3 NBJT .OP .TRAN 1U 5M .FOUR 1KHZ V(7) .MODEL NBJT NPN IS=1E-16 BF=100 VA=70 .PROBE V(7) .END *Problem 14.57 - Common-Emitter Amplifier 10mV VCC 6 0 DC 9 VEE 4 0 DC -9 VS 1 0 SIN(0 0.01 1K) C1 1 2 1U RB 2 0 10K RC 6 5 3.6K RE 3 4 2K C2 3 0 50U C3 5 7 1U R3 7 0 10K Q1 5 2 3 NBJT .OP .TRAN 1U 5M .FOUR 1KHZ V(7) .MODEL NBJT NPN IS=1E-16 BF=100 VA=70 .PROBE V(7) .END *Problem 14.57 - Common-Emitter Amplifier 15mV VCC 6 0 DC 9 VEE 4 0 DC -9 VS 1 0 SIN(0 0.015 1K) C1 1 2 1U RB 2 0 10K
-
14-466
RC 6 5 3.6K RE 3 4 2K C2 3 0 50U C3 5 7 1U R3 7 0 10K Q1 5 2 3 NBJT .OP .TRAN 1U 5M .FOUR 1KHZ V(7) .MODEL NBJT NPN IS=1E-16 BF=100 VA=70 .PROBE V(7) .END
Results: 1 kHz 2 kHz 3 kHz THD
5 mV 5.8 mV 0.335 mV (5.7%) 0.043 mV (0.74% 5.9% 10 mV 12.4 mV 1.54 mV (12.5%) 0.258 mV (2.1%) 12.8% 15 mV 20.6 mV 4.32 mV (21%) 1.18 mV (5.4%) 22%
14.58
*Problem 14.58 - Output Resistance VCC 2 0 DC 10 IB1 0 1 DC 10U Q1 2 1 0 NBJT IB2 0 3 DC 10U RE 4 0 10K Q2 2 3 4 NBJT .OP .DC VCC 10 20 .025 .MODEL NBJT NPN IS=1E-16 BF=60 VA=20 .PRINT DC IC(Q1) IC(Q2) .PROBE IC(Q1) IC(Q2) .END
Results: A small value of Early voltage has been used deliberately to accentuate the results. Note that the transistors have significantly different values of βF because of the collector-emitter voltage differences and low value of VA.
NAME Q1 Q2 MODEL NBJT NBJT IB 1.00E-05 1.00E-05 IC 8.77E-04 6.72E-04 VBE 7.61E-01 7.61E-01 VBC -9.24E+00 -2.41E+00 VCE 1.00E+01 3.18E+00 BETADC 8.77E+01 6.72E+01 GM 3.39E-02 2.60E-02 RPI 2.59E+03 2.59E+03 RO 3.33E+04 3.33E+04
-
14-467
From SPICE : Rout1 =20−10( )
1.17 − 0.877( )VmA
= 34.1 kΩ | Rout2 =20−10( )
903− 673( )VµA
= 43.5 kΩ
For circuit 1 : Rout1 = ro1 = 33.3 kΩ
For circuit 2 : Rout2 = ro 2 1+βoRE
Rth + rπ + RE
+ Rth + rπ( ) RE (See Eq. 14.28)
But Rth = ∞ → Rout2 = ro2 + RE = 33.3kΩ + 10kΩ = 43.3 kΩ
14.59
v th = GmRth = −gm
1 + gmRSro 1+ gmRS( )[ ]v i = −µ f v i = − 0.5mS( ) 250kΩ( )v i = −125v i
Rth = ro 1+ gmRS( ) = ro + µ f RS = 250kΩ + 125 18kΩ( )= 2.50 MΩ
14.60
v th = v irπ
RI + rπ1 + gmro( )=
rπRI + rπ
1+ µ f( )v i = 50kΩ270Ω + 50kΩ 1 + 2mS 250kΩ( )[ ]v i = 498v i
Rth ≅ ro 1+βoRI
RI + rπ
= 250kΩ 1+
100 270Ω( )270Ω + 50kΩ
= 384 kΩ
14.61
v th = v iβo + 1( )ro
RI + rπ + βo +1( )ro= v i
1RI
βo +1( )ro+
rπβo + 1( )ro
+ 1= v i
1gmRI
βo +1( )µ f+
βoβo +1( )µ f
+1≅ v i
Rth ≅RI + rπβo +1
ro ≅RI + rπβo + 1
14.62
a( ) y21 =i2v1 v2 =0
| i2 = −gmv1 | y21 = −gm | y12 =i1v2 v1 = 0
| i1 = 0 | y12 = 0 | y12y21
= 0
b( ) y21 = −400 µS | y12 = 0 | y21 >> y12
14.63
a( ) z21 =v2i1 i2 = 0
| v2 = i1RB( )βo + 1( )RE
RB + rπ + βo + 1( )RE | z21 =
βo + 1( )RERBRB + rπ + βo + 1( )RE
z12 =v1i2 i1 =0
=RE
RE +RB + rπβo + 1( )
RBβo +1( )
=RE RB
RB + rπ + βo + 1( )RE | z21 = βo + 1( )z12
b( ) z21 =101( ) 2.4kΩ( )150kΩ( )
2.4kΩ+ 10kΩ+ 101( )150kΩ= 2.40 kΩ | z12 =
z21101
= 23.7 Ω
14.64
-
14-468
a( ) h21 =i2i1 v2= 0
=−αoRE
RE +rπ
βo + 1
=−βoRE
rπ + βo + 1( )RE≅ −1
h12 =v1v2 i1= 0
=go
gm + gπ + go + gE=
1
µ f +µ fβo
+ 1+µ f
gmRE
≅1
µ f | h21 = −µ f h12
b( ) h21 =−100 3.9kΩ( )
33.3kΩ + 101( )3.9kΩ= −0.922 | h12 =
1
2400 +2400100
+ 1+240011.7
= 3.8x10−4
14.65
a( ) g21 =v2v1 i2= 0
= +gmRD | g12 =i1i2 v1 = 0
= −RD
RD + ro | g21 = −gm RD + ro( )g12 ≅ −µ f g12
b( ) g21 = +0.5mS 100kΩ( )= 50 | g12 = −100kΩ
100kΩ + 500kΩ= −0.167
14.66
a( ) y21 =i 2v1 v 2= 0
| i 2 =βo
rπ + βo + 1( )REv1 | y21 =
βorπ + βo + 1( )RE
y12 =i1v2 v 1= 0
| i1 = −i2RE
RE + rπ= − v2
Rout
RERE + rπ
≅ − v2
ro 1+βoRE
RE + rπ
RERE + rπ
y12 ≅ −1
βo +1( )ro for βo +1( )RE >> rπ
y12y21
= −1
βo + 1( )rorπ + βo + 1( )RE
βo≅
REβoro
for βo +1( )RE >> rπ | REβoro
=gmREβoµ f
-
14-469
At the output node vo : gmvx = go + GL( )vo − govx | vo =gm + gogo + GL
vx
ix = gmvx + go vx − vo( ) | ixvx
= gm + go 1−gm + gogo + GL
= gm + go
GL − gmgo + GL
ixvx
= gm + goGL − gmgo + GL
= GL
gm + gogo + GL
| Rin =vxix
=1gm
1+RLro
1+1µf
≅1gm
1+RLro
14.69
IC =1005 − 0.7
104 +101 103( )= 3.87mA | gm = 40IC = 0.155S | rπ =
100gm
= 645Ω
RL = 1kΩ 20kΩ = 952Ω | RE = 1kΩ 20kΩ = 952Ω
Av1 = −βoRL
rπ + βo + 1( )RE= −
100 952Ω( )645Ω +101 952Ω( )
= −0.984
Av2 =βo + 1( )RE
rπ + βo + 1( )RE=
101 952Ω( )645Ω +101 952Ω( )
= 0.993
The small - signal requirement limits the output signal to :
vbe = v i − vo2 = vi 1− 0.993( )= 0.007v i | v i ≤0.0050.007
= 0.714V
vo1 ≤ 0.984 0.714V( )= 0.703VWe also need to check VCB : VC = 5 − 3.87mA 1kΩ( )= 1.13V and VB = −104 IB = −0.387V .The total collector - base voltage of the transistor is therefore : VCB = 1.52V − 0.984v i − v i .We require VCB ≥ 0 for forward - active region operation. Therefore : v i ≤ 0.766 V .The small - signal limit is the most restrictive.
14.70
*Problem 14.70 - Common-Collector Amplifier 14.48(a) VCC 6 0 DC 18 VEE 7 0 DC -18 VI 1 0 AC 1 *For Output Resistance *VI 1 0 AC 0 *VO 8 0 AC 1 RI 1 2 500 C1 2 3 10UF R1 3 0 51K R2 6 3 100K RE 4 7 4.7K RC 6 5 2K C3 5 0 10UF C2 4 8 47UF R3 8 0 24K Q1 5 3 4 NBJT
-
14-470
.OP
.AC LIN 1 10KHZ 10KHZ
.MODEL NBJT NPN IS=1E-16 BF=125 VA=50
.PRINT AC VM(8) VP(8) VM(3) VP(3) IM(VI) IP(VI) IM(C2) IP(C2)
.END
Results: Q-point: (4.67 mA, 4.57 V), Av = 0.982, Rin = 31.1 kΩ???Rout?= 9.12 Ω
rπ =125 0.025V( )
4.67mA= 669Ω | ro =
50+ 4.57( )V4.67mA
= 11.7kΩ
RB = R1 R2 = 51kΩ 100kΩ = 33.8kΩ | RL = R3 RE ro = 24kΩ 4.7kΩ 11.7kΩ = 2.94kΩ
Rin = RB rπ + βo + 1( )RL[ ]= 33.8kΩ 669Ω + 126( )2.94kΩ[ ]= 31.0 kΩ
Av = +βo +1( )RL
rπ + βo +1( )RLRin
RI + Rin
=
126 2.94kΩ( )0.669kΩ +126 2.94kΩ( )
31.0kΩ500Ω+ 31.0 kΩ
= 0.982
Rout = RERB RI( )+ rπ
βo + 1= 4.7kΩ
33.8kΩ 500Ω( )+ 669Ω126
= 9.22 Ω
14.71
*Problem 14.71 - Common-Emitter Amplifier - 14.48(c) VCC 6 0 DC 12 VI 1 0 AC 1 *VI 1 0 AC 0 *VO 7 0 AC 1 RI 1 2 1K C1 2 3 2.2UF R1 6 3 20K R2 3 0 62K RE 6 4 3.9K C2 6 4 47UF RC 5 0 8.2K C3 5 7 10UF R3 7 0 100K Q1 5 3 4 PBJT .OP .AC LIN 1 5KHZ 5KHZ .MODEL PBJT PNP IS=1E-16 BF=75 VA=60 .PRINT AC VM(7) VP(7) VM(3) VP(3) IM(VI) IP(VI) IM(C3) IP(C3) .END
Results: Q-point: (525 µA, 5.62V), Av = -110, Rin = 3.16kΩ? ?Rout?= 7.69 kΩ
ro =60 + 5.62525x10−6
= 125kΩ | rπ =75 0.025( )525x10−6
= 3.57kΩ
RL = ro 8.2kΩ 100kΩ =125kΩ 8.2kΩ 100kΩ = 7.15kΩ
Rin = 15.1kΩ 3.57kΩ = 2.88 kΩ | Rout = ro 8.2kΩ = 7.70 kΩ | gm = 40IC = 21.0 mS
Av = −gmRLRin
RI + Rin
= − 21.0mS( ) 7.15kΩ( ) 2.88kΩ
1kΩ+ 2.88kΩ
= −111
14.72
-
14-471
*Problem 14.72 - Common-Source Amplifier - 14.48(d) VDD 4 0 DC 18 VI 1 0 AC 1 *For output resistance *VI 1 0 AC 0 *VO 7 0 AC 1 RI 1 2 1K C1 2 3 2.2U R1 3 0 500K R2 4 3 1.4MEG R4 6 0 27K C2 6 0 47U RD 4 5 75K C3 5 7 10U R3 7 0 470K M1 5 3 6 6 NMOSFET .OP .AC LIN 1 5KHZ 5KHZ .MODEL NMOSFET NMOS VTO=1 KP=250U LAMBDA=0.02 .PRINT AC VM(3) VP(3) VM(7) VP(7) IM(VI) IP(VI) IM(C3) IP(C3) .END
Results: Q-point: (106µA, 7.14V), Av = -14.2, Rin = 369kΩ, Rout = 65.8 kΩ
ro =50 + 7.14106x10−6
= 539kΩ | gm = 2 250x10−6( )106x10−6( )1+ 0.02 7.14( )[ ]= 246µS
RL = ro RD 470kΩ = 539kΩ 75kΩ 470kΩ = 57.7kΩ
Rin = R1 R2 = 500kΩ 1.4MΩ = 368kΩ | Rout = ro 75kΩ = 65.8 kΩ
Av = −gmRLRin
RI + Rin
= − 0.246mS( ) 57.7kΩ( ) 368kΩ
1kΩ + 368kΩ
= −14.2
14.73 *Problem 14.73 - Common-Gate Amplifier - 14.48(e) VSS 5 0 DC 12 VDD 6 0 DC -12 VI 1 0 AC 1 *For Output Resistance *VI 1 0 AC 0 *VO 7 0 AC 1 RI 1 2 500 C1 2 3 10U R1 5 3 33K RD 6 4 24K C2 4 7 47U R3 7 0 100K M1 4 0 3 3 PFET .OP
-
14-472
.AC LIN 1 50KHZ 50KHZ
.MODEL PFET PMOS KP=200U VTO=-1 LAMBDA=0.02
.PRINT AC VM(7) VP(7) VM(3) VP(3) IM(VI) IP(VI) IM(C2) IP(C2)
.END Results: Q-point: (286 µA, 7.72V), Av = +5.50, Rin = 2.73 kΩ, Rout = 21.8 kΩ
gm = 2 2x10−4( ) 2.86x10−4( )1+ 0.02 7.72( )[ ]= 3.63x10−4 S | R I RS = 0.5kΩ 33kΩ = 493Ω
ro =50+ 7.722.86x10−4
= 202kΩ | RL = ro RD R3 = 202kΩ 24kΩ 100kΩ = 17.7kΩ | Rin = RS1gm
= 2.54 kΩ
Rout = ro RD = 21.4 kΩ | Av =gmRL
1+ gm RI RS( )RS
RI + RS
=
0.363mS 17.7kΩ( )1+ 0.363mS 0.493kΩ( )
33kΩ500Ω+ 33kΩ
= 5.37
14.74
IC =1005 − 0.7
500kΩ+ 500kΩ + 101( )430kΩ= 9.68µA | VCE = 5 − IC 430kΩ( )− −5( )= 5.80V
rπ =100
40 9.68µA( )= 258kΩ | ro =
60 +5.89.68x10−6
= 6.80MΩ | RL = 500kΩ 430kΩ 500kΩ ro = 154kΩ
Absorb R1 inro the transistor : rπ' = rπ R1 =170kΩ | βo
' = gmrπ' = 65.8
Rin = rπ' + βo
' + 1( )RL =170kΩ + 66.8 154kΩ( )=10.5 MΩ
Rout = 430kΩ 500kΩ roRI + rπ
'
βo' +1
= 2.53 kΩ
Av = +βo
' + 1( )RLRI + rπ
' + βo' +1( )RL
=66.8 154 kΩ( )
0.5kΩ+ 170kΩ+ 66.8 154kΩ( )= 0.984
*Problem 14.74 - Common-Collector Amplifier - 14.1(f) VCC 7 0 DC 5 VEE 8 0 DC -5 VI 1 0 AC 1 *For Output Resistance *VI 1 0 AC 0 *VO 6 0 AC 1 RI 1 2 500 C1 2 3 10UF R1 3 5 500K R2 5 0 500K RE 4 8 430K C2 4 5 47UF C3 4 6 10UF R3 6 0 500K Q1 7 3 4 NBJT .OP
-
14-473
.AC LIN 1 10KHZ 10KHZ
.MODEL NBJT NPN IS=1E-16 BF=100 VA=60
.PRINT AC VM(6) VP(6) VM(3) VP(3) IM(VI) IP(VI) IM(C3) IP(C3)
.END
Results: Q-point: (9.81 µA, 5.74V), Av = 0.983, Rin = 11.0 MΩ???Rout?= 2.58 kΩ
14.75 *Problem 14.75 - Common-Source Amplifier - 14.48(g) VDD 6 0 DC 20 VI 1 0 AC 1 *For output resistance *VI 1 0 AC 0 *VO 7 0 AC 1 RI 1 2 500 C1 2 3 2.2UF RG 3 0 1MEG R4 4 0 11K C2 5 7 47UF RD 6 5 39K R3 7 0 500K J1 5 3 4 NJFET .OP .AC LIN 1 4KHZ 4KHZ .MODEL NJFET NJF BETA=1.25M VTO=-4 LAMBDA=0.02 .PRINT AC VM(3) VP(3) VM(7) VP(7) IM(VI) IP(VI) IM(C2) IP(C2) .END
Results: Q-point: (319 µA, 4.03V), Av = -3.02, Rin = 1.00 MΩ, Rout = 38.4 kΩ
VGS = − 11kΩ( )ID = − 11kΩ( ) 20mA( ) 1−VGS−4
2
→ VGS = −3.50V , ID = −VGS
11kΩ= 318 µA
VDS = 20− ID 11kΩ + 39kΩ( )= 4.10V | Active region operation is correct.
gm =2−4
20mA 318µA( ) = 1.26mS | Assume λ = 0, ro = ∞. | RL = 39kΩ 500kΩ = 36.2kΩ
14.76
*Problem 14.76 - Common-Base Amplifier - 14.48(h) VCC 7 0 DC -9 VEE 4 0 DC 9 VI 1 0 AC 1 *For output resistance *VI 1 0 AC 0 *VO 8 0 AC 1 RI 1 2 500 C2 2 3 47UF RB 5 0 100K RE 3 4 82K C1 5 0 4.7UF RC 7 6 39K C3 6 8 10UF
-
14-474
R3 8 0 100K Q1 6 5 3 PBJT .OP .AC LIN 1 12KHZ 12KHZ .MODEL PBJT PNP IS=1E-16 BF=50 VA=50 .PRINT AC VM(3) VP(3) VM(8) VP(8) IM(VI) IP(VI) IM(C3) IP(C3) .END
Results: Q-point: (97.2 µA, 6.10V), Av = 35.5, Rin = 273 Ω??Rout?= 38.1 kΩ
gm = 40IC = 3.89mS | rπ =βogm
= 12.9kΩ | ro =50 + 6.10( )V
97.2µA= 577kΩ
Rth = RI RE = 0.5kΩ 82kΩ = 497Ω | RL = ro 1+ gmRth( ) RC R3 = 1.69MΩ 39kΩ 100kΩ = 27.6kΩ
Av =gmRL
1+ gm RI RE( )RE
RI + RE
=
3.89mS 27.6kΩ( )1+ 3.89mS 497Ω( )
82kΩ500Ω+ 82kΩ
= 36.4
Rin = 82kΩrπ
βo +1= 252Ω | Rout = ro 1+ gmRth( ) RC = 38.1 kΩ
-
14-475
14.77 *Problem 14.77 - Common-Source Amplifier 14.48(j) VDD 6 0 DC 18 VI 1 0 AC 1 *For output resistance *VI 1 0 AC 0 *VO 7 0 AC 1 RI 1 2 1K C1 2 3 2.2UF R2 6 3 2.2MEG R1 3 0 2.2MEG RS 6 4 22K C2 6 4 47UF RD 5 0 18K C3 5 7 10UF R3 7 0 470K M1 5 3 4 4 PFET .OP .AC LIN 1 7.5KHZ 7.5KHZ .MODEL PFET PMOS KP=400U VTO=-1 LAMBDA=0.02 .PRINT AC VM(3) VP(3) VM(7) VP(7) IM(VI) IP(VI) IM(C3) IP(C3) .END
Results: Q-point: (268µA, 8.60V), Av = -8.29, Rin = 1.10 MΩ??Rout?= 16.4 kΩ
ro =50 + 8.60268x10−6
= 219kΩ | gm = 2 400x10−6( )268x10−6( )1+ 0.02 8.60( )[ ]= 501µS
RL = ro RD 470kΩ = 219kΩ 18kΩ 470kΩ =16.1kΩ
Rin = R1 R2 = 2.2MΩ 2.2MΩ = 1.1 MΩ | Rout = ro 18kΩ = 16.6 kΩ
Av = −gmRLRin
RI + Rin
= − 0.501mS( )16.1kΩ( ) 1.1MΩ
1kΩ+ 1.1MΩ
= −8.06
14.78
*Problem 14.78 - Common-Gate Amplifier - 14.48(k) VDD 5 0 DC 15 VI 1 0 AC 1 *For output resistance *VI 1 0 AC 0 *VO 6 0 AC 1 RI 1 2 1K C1 2 3 2.2U R1 3 0 3.9K RD 4 5 20K C2 4 6 47U RS 6 0 51K M1 4 0 3 3 NMOSFET .OP .AC LIN 1 20KHZ 20KHZ .MODEL NMOSFET NMOS VTO=-2 KP=500U LAMBDA=0.02 .PRINT AC VM(3) VP(3) VM(6) VP(6) IM(VI) IP(VI) IM(C2) IP(C2) .END
Results: Q-point: (268µA, 8.60V), Av = 4.26, Rin = 1.27 kΩ???Rout?= 18.8 kΩ
-
14-476
gm = 2 5x10−4( ) 268x10−6( )1+ 0.02 8.60( )[ ]= 0.560mS | Rin = 3.9kΩ 1gm
= 1.22kΩ
ro =50 + 8.60268x10−6
= 219kΩ | Rth = RI RS = 981Ω
Rout = ro 1+ gmRth( ) RD = 18.9 kΩ | RL = Rout 51kΩ = 13.8kΩ
Av =gmRL
1+ gm RI RS( )RS
RI + RS
=
0.560mS 13.8kΩ( )1+ 0.560mS 0.981kΩ( )
3.9kΩ1kΩ+ 3.9kΩ
= 3.97
14.79 *Problem 14.79 - JFET Common-Source Amplifier - 14.48(m) VDD 5 0 DC -16 VI 1 0 AC 1 *For output resistance *VI 1 0 AC 0 *VO 6 0 AC 1 RI 1 2 5K C1 2 3 2.2U R1 3 0 10MEG RD 4 5 1.8K C2 4 6 10U R3 6 0 36K J1 4 3 0 PJFET .OP .AC LIN 1 3KHZ 3KHZ .MODEL PJFET PJF BETA=200U VTO=-5 LAMBDA=0.02 .PRINT AC VM(3) VP(3) VM(6) VP(6) IM(VI) IP(VI) IM(C2) IP(C2) .END
Results: Q-point: (5.59 ?A, 5.93 V), Av = -3.27, Rin = 10.0 MΩ?? Rout?= 1.53 kΩ
gm =2
−55mA 5.59mA( ) = 2.11mS | ro =
50 + 5.935.59x10−3
=10.0kΩ
Av = -gmRLRG
RI + RG
= − 2.11mS( ) 10.0kΩ 1.8kΩ 36kΩ( ) 10MΩ
10MΩ + 5kΩ
= −3.09
Rin = 10.0 MΩ | Rout = RD ro = 1.53 kΩ
14.80 *Problem 14.69 - Common-Emitter Amplifier - 14.48(n) VCC 7 0 DC 10 VEE 6 0 DC -10 VI 1 0 AC 1 *For output resistance *VI 1 0 AC 0 *VO 8 0 AC 1 RI 1 2 250 C1 2 3 4.7UF RB 3 0 20K R4 4 6 9.1K C2 4 0 100UF L 7 5 1H C3 5 8 1UF
-
14-477
R3 8 0 1MEG Q1 5 3 4 NBJT .OP .AC LIN 1 500KHZ 500KHZ .MODEL NBJT NPN IS=1E-16 BF=80 VA=100 .PRINT AC VM(3) VP(3) VM(8) VP(8) IM(VI) IP(VI) IM(C3) IP(C3) .END
Results: Q-point: (979 µA, 11.0 V), Av = -3420, Rin = 2.09 kΩ???Rout?= 113 kΩ
rπ =80 0.025V( )
979µA= 2.04kΩ | ro =
100 +11.0( )V979µA
=113kΩ | Rout = ro =113 kΩ
RL = ro 1MΩ =113kΩ 1MΩ =102kΩ | Rin = RB rπ = 20kΩ 2.04kΩ = 1.85 kΩ
Av = -gmRLRin
RI + Rin
= −40 979µA( ) 102kΩ( ) 1.85kΩ
250Ω+ 1.85kΩ= −3520
14.81 *Problem 14.81 - Source Follower - 14.48(o) VDD 5 0 DC 5 VSS 6 0 DC -5 VI 1 0 AC 1 *For output resistance *VI 1 0 AC 0 *VO 7 0 AC 1 RI 1 2 10K C1 2 3 2.2U R1 3 0 1MEG L 4 6 100mH C3 4 7 4.7U R3 7 0 100K M1 5 3 4 4 NMOSFET .OP .AC LIN 1 100KHZ 100KHZ .MODEL NMOSFET NMOS VTO=1 KP=400U LAMBDA=0.02 .PRINT AC VM(3) VP(3) VM(7) VP(7) IM(VI) IP(VI) IM(C3) IP(C3) .END
Results: Q-point: (3.84 mA, 10.0 V), Av = 0.953, Rin = 1.00 MΩ?? Rout?= 504 Ω
gm = 2 4x10−4( ) 3.84x10−3( )1+ 0.02 10( )[ ]=1.92mS
ro =
10.02
+ 10
3.84VmA
= 15.6kΩ − Cannot neglect! | RL =15.6kΩ 100kΩ =13.5kΩ
Rin = RG =1 MΩ | Rout =1gm
ro = 504 Ω
Av = +Rin
RI + Rin
gmRL1+ gmRL
= +
1MΩ10kΩ + 1MΩ
1.92mS 13.5kΩ( )1+ 1.92mS 13.5kΩ( )
= 0.953
-
14-478
14.82
a( ) VEQ =18500 kΩ
1.4MΩ + 500kΩ= 4.74V | REQ = 500kΩ 1.4 MΩ = 368kΩ
4.74 =VGS + 27000 ID =1+2IDS
250 x10−6+ 27000 ID → ID =104µA
VDS =18 − ID 75kΩ+ 27kΩ( )= 7.39V | Active region operation is correct.
gm = 2 250 x10−6( )104 x10−6( )= 0.228mS | ro = 50 + 7.39104 µA = 552kΩ | RG = R1 R2 = 368 kΩ
C1 ≥101
2πf RI + RG( )= 10
2π 400Hz( ) 1kΩ + 368kΩ( ) | C1 ≥ 0.0108 µF → 0.01 µF
C2 ≥101
2πf RS1
gm
= 10
2π 400Hz( ) 27kΩ 10.228 mS
| C2 ≥ 1.05 µF →1.0 µF
C3 ≥101
2πf RD ro( )+ R3[ ]= 10
2π 400Hz( ) 66.0kΩ + 470kΩ( ) | C3 ≥ 7.42 nF → 8200 pF
b( ) C2 =1
2πf RS1
gm
=1
2π 2000 Hz( ) 27kΩ 10.228mS
= 0.0211 µF → 0.022 µF
14.83
a( ) VEQ = 1262kΩ
20kΩ + 62kΩ= 9.07V | REQ = 20kΩ 62kΩ = 15.1kΩ
IB =12 − 0.7 − 9.07( )V
15.1kΩ + 75 + 1( )3.9kΩ= 7.16µA | IC = 537 µA | VEC = 12− 3900IE − 8200IC = 5.47 V
Active region is correct.
rπ =75 0.025V( )
537µA= 3.49kΩ | ro =
60+ 5.47537µA
= 122kΩ | gm = 40IC = 21.5 mS
Rin = R1 R2 rπ = 15.1kΩ 3.49kΩ = 2.83 kΩ | Rout = ro RC = 122kΩ 8.2kΩ = 7.68 kΩ
C1 ≥ 101
2πf RI + Rin( )= 10
2π 100Hz( )1kΩ+ 2.83kΩ( ) | C1 ≥ 4.16 µF → 0.01 µF
C2 ≥ 101
2πfRI REQ + rπ
βo +1
=10
2π 100Hz( )1kΩ 15.1kΩ + 3.49kΩ
76
| C2 ≥ 273 µF → 270 µF
C3 ≥ 101
2πf Rout + R3[ ]=
102π 100Hz( ) 7.68kΩ +100kΩ( )
| C3 ≥ 0.148 µF → 0.15 µF
b( ) C2 =1
2πfRI REQ + rπ
βo +1
=1
2π 1000Hz( )1kΩ 15.1kΩ + 3.49kΩ
76
= 2.73 µF → 2.7 µF
14.84
-
14-479
IC =1005− 0.7
104 +101 103( )= 3.87mA | gm = 40IC = 0.155S | rπ =
100gm
= 645Ω | ro = ∞
The capacitors will be negligible at a frequency 10 times the individual break frequencies :
Req1 =10kΩ rπ + βo + 1( ) 1kΩ 20kΩ( )[ ]= 9.06kΩ | f1 = 102π 9.06kΩ( )2µF = 87.8 Hz
Req2 = 20kΩ + 1kΩrπ
βo + 1( )
= 20.0kΩ | f 2 =
102π 20.0kΩ( )10µF
= 7.96 Hz
Req3 = Rout + 20kΩ = 21.0kΩ | f 3 =10
2π 21.0kΩ( )10µF= 7.56 Hz
14.85
a( ) IC = αF IE =8081
5 − 0.713.3x103
= 319µA | gm = 40IC = 12.8mS | rπ =
80gm
= 6.26kΩ | ro = ∞
Req1 = 75Ω + 13.3kΩrπ
βo + 1( )
= 152Ω | C1 =
102π 50kHz( )152Ω
= 0.209 µF → 0.20 µF
Req2 = Rout +100kΩ = 8.25kΩ +100kΩ = 108kΩ | C2 =10
2π 50kHz( )108kΩ= 295 pF → 270 pF
b( ) C1 = 0.209µF50kHz100Hz
=105 µF →100 µF | C2 = 295pF
50kHz100Hz
= 0.148 µF → 0.15 µF
14.86
VEQ =1851kΩ
51kΩ + 100kΩ= 6.08V | REQ = 51kΩ 100kΩ = 33.8kΩ
IB =6.08 − 0.7 + 18( )V
33.8kΩ + 126( ) 4.7kΩ( )= 37.3µA | IC = 4.67 mA | VCE = 36 − 2000IC − 4700IE = 4.54 V
Active region is correct. | rπ =125 0.025V( )
4.67mA= 669Ω | ro =
50 + 4.54( )V4.67mA
= 11.7kΩ
RB = R1 R2 = 51kΩ 100kΩ = 33.8kΩ | RL = R3 RE ro = 24kΩ 4.7kΩ 11.7kΩ = 2.94kΩ
Rin = RB rπ + βo +1( )RL[ ]= 33.8kΩ 669Ω + 126( )2.94kΩ[ ]= 31.0 kΩ
Rout = RERB RI( )+ rπ
βo +1= 4.7kΩ
33.8kΩ 500Ω( )+ 669Ω126
= 9.22 Ω
C1 =10
2πf RI + Rin( )= 10
2π 100Hz( ) 500Ω + 31.0kΩ( )= 0.505µF → 0.50 µF
C2 =10
2πf R3 + Rout( )=
102π 100Hz( ) 24kΩ + 9.22Ω( )
= 0.663µF → 0.68 µF
-
14-480
14.87 Note : RS ≡ R1 = 3.9kΩ
VGS = −3900ID = −39005x10−4( )
2VGS + 2( )
2 | VGS = −0.975 VGS + 2( )
2→ VGS = −0.9915V
ID =5x10−4( )
2VGS + 2( )
2 = 254µA | VDS =15 − 23.9kΩID = 8.92V - Pinched off.
gm =2 254µA( )2 − 0.992
= 0.504mS | ro =50 + 8.92254 x10−6
= 232kΩ | Rin = 3.9kΩ1
gm= 1.32kΩ
Rout = RD ro 1 + gm RS RI( )[ ]= 20kΩ 232kΩ 1 + 0.504mS 3.9kΩ 1kΩ( )[ ]=18.8kΩC1 =
102πf RI + Rin( )
= 102π 400Hz( )1kΩ+ 1.32kΩ( )
=1.72µF →1.8 µF
C2 =10
2πf R3 + Rout( )=
102π 400Hz( ) 51kΩ +18.8Ω( )
= 0.057µF → 0.056 µF
14.88
a( ) Use C2 to set the lower cutoff frequency to 1 kHz. C1 and C3 remain negligible at 1 kHz.C2 = 0.056 µF , C1 = 1800 pF, C3 = 0.015 µF
(b) SPICE Results: fL = 925 Hz
14.89
a( ) Use C3 to set the lower cutoff frequency to 2 kHz. C1 remains negligible at 2 kHz.C1 = 8200 pF, C3 = 820 pF
b( ) Use C1 to set the lower cutoff frequency to 1 kHz. C2 and C3 remain negligible at 1 kHz.C1 = 0.042 µF , C2 = 1800 pF, C3 = 0.015 µF
(c) SPICE Results: For (a) fL = 1.96 kHz. For (b) fL = 1.02 kHz
14.90
Av =gmRL
1+ gmRL≥ 0.95 → gmRL ≥ 19 | gm = 2KnID | VGS − VTN =
2IDKn
= 0.5V
ID =0.5( )2 0.03( )
2= 3.75mA | RL ≥
192 0.03( ) 0.00375( )
=1.27kΩ
RL = RS 3kΩ → RS ≥ 2.19kΩ | VSS = VGS + 3.75mA( )RS | Possible designs :2.4kΩ, 11.5V ; 2.7kΩ, 12.6V ; 3.0kΩ, 13.75V - Making a choice which uses a nearly minimum value of supply voltage gives : VSS = 12 V ,RS = 2.4 kΩ.
-
14-481
14.91 For a common-emitter amplifier with RE = 0,
Rin ≅ rπ =βoVT
IC | IC =
100 0.025V( )75Ω
= 33.3 mA
14.92
Using Eqn. 14.102 : 50 =RE
1+ 40 4.3( )→ RE = 8.65kΩ | IC ≅
4.3VRE
= 497µA
50 = gmRLRin
RI + Rin | Assuming RI = 50Ω, 50 =
gmRL2
→ RL =2 50( )
40 497µA( )= 5.03kΩ
RL = RC 100kΩ → RC = 5.30kΩ | VEC = 5 + 0.7 − IC RC = 3.07V - Active region is ok.
C1 >>1
2π 500kHz( ) 50Ω + 50Ω( )= 3.18nF → C1 = 0.033 µF
C2 >>1
2π 500kHz( )105kΩ( )= 3.02pF → C2 = 33 pF
14.93 The base voltage should remain half way between the positive and negative power supply voltages. If VEE = +10V and VCC = 0V, then VB should = 5 V which can be obtained using a resistive voltage divider from the +10V supply. We now have the standard four-resistor bias circuit. The base current is 327 µA/80 = 4 µA.
vS 100 k Ω
+
-
vO
75 Ω
C1
+ 10 V
13 k Ω 8.2 k Ω
R1 R2
C2
CB
R ER C
120 k Ω 110 k Ω
Setting the current in R 1 to 10IB = 40µA, R1 =5V
40µA= 125kΩ →120kΩ. The
current in R 2 =11IB = 44µA, and R 2 =5V
44µA= 114kΩ → 110kΩ.
Note that the base terminal must now be bypassed with a capacitor.
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14.94
Using Eqn. 14.102 : 75 =RE
1+ 40 8.3( )→ RE = 25.0kΩ | IC ≅
8.3VRE
= 332µA
50 = gmRLRin
RI + Rin | 50 =
gmRL2
→ RL =2 50( )
40 332µA( )= 7.52kΩ | RL = RC 100kΩ → RC = 8.13kΩ
VEC = 9 + 0.7 − IC RC = 6.98V - Active region is ok.
C1 >>1
2π 500kHz( ) 75Ω + 75Ω( )= 2.12nF → C2 = 0.022 µF
C2 >>1
2π 500kHz( )108kΩ( )= 2.95 pF → C2 = 30 pF
14.95
Rin ≅1gm
→ gm = 2KnID = 0.1S | ID =0.012Kn
| a( ) ID =0.01
2 0.005( )=1 A
b( ) ID =0.01
2 0.5( )= 10.0 mA | The second FET achieves the desired input resistance
at much lower current and hence much lower power for a given supply voltage.
14.96 1
gm=
VTIC
=kTqIC
∝ T
At − 40oC = 233K , 1
gm= 50Ω
233k300K
= 38.8 Ω. | At + 50oC = 323K,
1gm
= 50Ω323K300K
= 53.8 Ω.
Another approach : At 27oC = 300K, IC =300k50q
=6kq
.
At − 40oC = 233K , 1
gm=
2336
= 38.8 Ω. | At + 50oC = 323K, 1
gm=
3236
= 53.8 Ω.
14.97
This analysis assumes that the source and load resistors are fixed, and that only
the amplifier parameters are changing. Av = gmRLRin
RI + Rin
Since RE >> 75Ω, RE RI ≅ 75Ω and Rin ≅ RE1
gm≅
1gm
| Av ≅gmRL
1+ gmRITo achieve Av
max , RL → RLmax ,gm → gm
max which requires
IC → ICmax = 0.988
5.25 − 0.7( )V13kΩ 0.95( )
= 364µA | RLmax = 8.2kΩ 1.05( )100kΩ = 7.93kΩ
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14-483
gm = 40 364µA( ) =14.6mS | Avmax =14.6mS 7.93kΩ( )1+ 0.0146 75( )
= 55.3
To achieve A vmin , RL → RL
min , gm → gmmin which requires
IC → ICmin = 0.988
4.75 − 0.7( )V13kΩ 1.05( )
= 293µA | RLmin = 8.2kΩ 0.95( )100kΩ = 7.23kΩ
gm = 40 293µA( ) =11.7mS | Avmin =11.7mS 7.23kΩ( )1+ 0.0117 75( )
= 45.1 | 45.1≤ AV ≤ 55.3
The range is only slightly larger than that observed in the Monte Carlo analysis in Table 14.16.
14.98 *Problem 14.76 - Common-Base Amplifier - Monte Carlo Analysis *Generate Voltage Sources with 5% Tolerances IEE 0 8 DC 5 REE 8 0 RTOL 1 EEE 6 0 8 0 1 * ICC 0 9 DC 5 RCC 9 0 RTOL 1 ECC 7 0 9 0 -1 * VS 1 0 AC 1 RS 1 2 75 C1 2 3 47U RE 3 6 RTOL 13K Q1 4 0 3 PBJT RC 4 7 RTOL 8.2K C2 4 5 4.7U R3 5 0 100K .OP .AC LIN 1 10KHZ 10KHZ .PRINT AC VM(5) VP(5) .MODEL PBJT PNP (BF=80 DEV 25%) (VA = 60 DEV 33.33%) .MODEL RTOL RES (R=1 DEV 5%) .MC 1000 AC VM(5) YMAX .END
Results: Mean value Av = 47.5; 3σ limits: 42.5 = Av = 52.5. However, the worst-case values observed in the
analysis are Avmin = 43.2 and Av
max = 51.9. The mean is 5% lower than the design value. The width of the
distribution is approximately the same as that in Table 14.16.
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14.99 (a)
This analysis assumes that the source and load resistors are fixed, and that only
the amplifier parameters are changing. Av =gmRL
1+ gmRth
RERI + RE
Rth = RE RI and RE
RI + RE=
1
1+RIRE
where RE =13.3kΩ and RI = 75Ω
Since R E >> RI , Rth and RE
RI + REare essentially constant. To achieve Av
max , RL → RLmax ,gm → gm
max
which requires IC → ICmax = 0.988
5.10 − 0.7( )V13.3kΩ 0.99( )
= 330µA | RLmax = 8.25kΩ 1.01( )100kΩ = 7.69kΩ
gm = 40 330µA( )=13.2mS | Avmax =13.2mS 7.69kΩ( )
1+ 0.0132 75( )13.3 0.99( )
75 +13.3 0.99( )
= 50.7
To achieve Avmin , RL → RL
min ,gm → gmmin which requires
IC → ICmin = 0.988
4.90 − 0.7( )V13.3kΩ 1.01( )
= 309µA | RLmin = 8.25kΩ 0.99( )100kΩ = 7.55kΩ
gm = 40 309µA( )=12.4mS | Avmax =12.4mS 7.55kΩ( )1 + 0.0124 75( )
13.3 1.01( )75 + 13.3 1.01( )
= 48.2
(b) Using a Spreadsheet similar to Table 14.16: Mean value Av = 49.6; 3σ limits: 48.2 = Av = 50.9. The worst-case
values observed in the analysis are Avmin = 48.4 and Av
max = 50.8.
14.100 *Problem 14.100 - Common-Base Amplifier - Monte Carlo Analysis *Generate Voltage Sources with 2% Tolerances IEE 0 8 DC 5 REE 8 0 RTOL 1 EEE 6 0 8 0 1 * ICC 0 9 DC 5 RCC 9 0 RTOL 1 ECC 7 0 9 0 -1 * VS 1 0 AC 1 RS 1 2 75 C1 2 3 100U RE 3 6 RR 13.3K Q1 4 0 3 PBJT RC 4 7 RR 8.25K C2 4 5 1U R3 5 0 100K .OP .AC LIN 1 10KHZ 10KHZ .PRINT AC VM(5) VP(5) IM(VS) IP(VS) .MODEL PBJT PNP (BF=80 DEV 25%) (VA = 60 DEV 33.33%) .MODEL RTOL RES (R=1 DEV 2%)
-
14-485
.MODEL RR RES (R=1 DEV 1%)
.MC 1000 AC VM(5) YMAX *.MC 1000 AC IM(VS) YMAX .END
Results: Mean value: Av = 47.2; 3σ limits: 45.7 = Av = 48.5 Mean value: Rin = 83.4 Ω; 3σ limits: 79.5 Ω = Av = 87.6 Ω
14.101
Rin = RE1
gm=
RE1+ gmRE
=RE
1 + 40IC RE=
RE
1+ 408081
IE RE=
RE1+ 39.5IERE
IE RE = 2.5 − 0.7 = 1.8V | 75 =RE
1 + 39.5 1.8( )→ RE = 5.41kΩ
IC =8081
1.8V5.41kΩ
= 329µA | Rth = 75Ω 5.41kΩ = 74.0Ω | gm = 40 329µA( )= 13.2mS
Av =gmRL
1 + gmRth
RERI + RE
→ RL = 7.59kΩ
7.59kΩ = RC 100kΩ → RC = 8.21kΩ | VC = −2.5V + IC RC = +0.201V | Oops! We are violating
our definition of the forward - active region. If we use the nearest 5% values, RE = 5.6kΩ andRC = 8.2kΩ, IC = 318µA and VC = +0.108V . The transistor is just entering saturation.
14.102 Using a Spreadsheet similar to Table 14.14:
Mean value: Av = 0.960; 3σ limits: 0.942 = Av = 0.979
Mean value: ID = 4.91 mA; 3σ limits: 4.27 mA = ID = 5.55 mA
Mean value: VDS = 7.03 V; 3σ limits: 4.52 V = VDS = 9.54 V
*Problem 14.102 - Common-Drain Amplifier - Fig. 14.34 *Generate Voltage Sources with 5% Tolerances IDD 0 7 DC 5 RDD 7 0 RTOL 1 EDD 5 0 7 0 1 * ISS 0 8 DC 20 RSS 8 0 RTOL 1 ESS 6 0 8 0 -1 * VGG 1 0 DC 0 AC 1 C1 1 2 4.7U RG 2 0 RTOL 22MEG RS 3 6 RTOL 3.6K C2 3 4 68U R3 4 0 3K M1 5 2 3 3 NMOSFET .OP .AC LIN 1 10KHZ 10KHZ .DC VGG 0 0 1 .MODEL NMOSFET NMOS (VTO=1.5 DEV 33.33%) (KP=20M DEV 50%) LAMBDA=0.02
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.MODEL RTOL RES (R=1 DEV 5%)
.PRINT AC VM(4) VP(4) IM(VGG) IP(VGG)
.MC 1000 DC ID(M1) YMAX *.MC 1000 DC VDS(M1) YMAX *.MC 1000 AC IM(VGG) YMAX *.MC 1000 AC VM(4) YMAX .END
Results: Mean value: ID = 4.97 mA; 3σ limits: 4.32 mA = ID = 5.62 mA
Mean value: VDS = 7.19 V; 3σ limits: 6.18 V = VDS = 8.20 V
Mean value: Rin = 22.0 MΩ; 3σ limits: 20.3 Ω = Rin = 24.0 Ω
Mean value: Av = 0.956; 3σ limits: 0.936 = Av = 0.976
14.103
a( ) Avt =gmRL
1+ gm 1+ η( )RL=
0.01S 1kΩ( )1+ 0.01S 1+ 0.5( )1kΩ( )
= 0.625 | Rin = ∞
Rout =1
gm 1+ η( )=
10.01S 1+ 0.5( )
= 66.7Ω
Ai =gmRG
1+ gm 1+ η( )RL=
0.01S 1.5MΩ( )1+ 0.01S 1+ 0.5( )1kΩ( )
= 14.8kΩ
b( ) Avt and Ai are worse; Rout is improved.
14.104
a( ) Avt = −gmRL
1+ gm 1+ η( )R5= −
0.01S 2kΩ( )1+ 0.01S 1+ 0.75( ) 200Ω( )
= −4.44 | Rin = RG
Rout = ro 1+ gm 1+ η( )R5[ ]= 10kΩ 1+ 0.01S 1.75( ) 200Ω( )[ ]= 45.0 kΩ
Ai = −gmRG
1+ gm 1+ η( )R5= −
0.01S 1MΩ( )1+ 0.01S 1+ 0.75( ) 200Ω( )
= 2.22kΩ
b( ) Avt and Ai are reduced; Rout is increased.
14.105
a( ) Avt =gm 1+ η( )RL
1+ gm 1+ η( )Rth=
0.5mS 1+ 1( )100kΩ( )1+ 0.5mS 1+1( ) 50Ω( )
= 95.2
Rin = RS1
gm 1+ η( )= 100kΩ
10.5mS 1+1( )
= 990 Ω
Ai = gm 1+ η( )Rin = 0.990Rout = ro 1+ gm 1+ η( )Rth[ ]= ro 1+ 0.5mS 1+ 1( ) 50Ω( )[ ]= 1.05rob( ) Avt , Ai and Rout are larger; Rin is smaller.