First and Second Order Filters - Carleton Universityrmason/Teaching/486-d.pdf · First and Second...
Transcript of First and Second Order Filters - Carleton Universityrmason/Teaching/486-d.pdf · First and Second...
First and Second Order Filters
• These functions are useful for the design of simple filters or they canbe cascaded to form high-order filter functions
First Order Filters
General first order bilinear transfer function is given by:
T sa s as
o
o
( ) =+
+1
ω pole at s = - ωo and a zero at s = - ao / a1 and a high frequency gain that approaches a1
• The numerator coefficients (ao, a1) determine the type of filter (e.g.low-pass, high-pass, etc.)
Transfer Functions
Low Pass
High Pass
Bandpass
Notch
All Pass
T s LC
s s CR LC
T ss
s s Q
T ss CR
s s CR LC
T ss
s s Q
T ss Q
s s Q
( )
( )
( )
( )
( ) .
=+
+
=+
+
=
+
+
=+
+
+
= −
+
+
1
1 1
1
1 1
0 5
2
2
2 2
2
2 2
2 2
2 2
ω ω
ωω ω
ω
ω ω
οο
ο
οο
ο
οο
Consider the Following Circuit
t sN sD s
L s At sA N sD s
( )( )
( )( ) ( )
( )
( )= = = =Loop Gain
For stability. 1+ L (s) = 0 which results in the poles sP of the closed - loop circuit as
t sAP( ) = −1
Assuming an ideal opamp with A = ∞ the poles are obtained from
N sP( ) = 0
• That is, the poles are identical to the zeros of the RC network• Since our objective is to realize a pair of complex conjugate poles
we should select an RC network that has complex conjugate zeros• The simplest such networks are Bridged - T networks
• The pole polynomial of the active filter circuit will be equal to thenumerator polynomial of the Bridged - T network
s sQ
sC C R C C R R
C C R RQ
C C R R
R C C
2 2 2
1 2 3 1 2 3 4
1 2 3 4
1 2 3 4
3 1 2
1
1 1 1 1
1 1 1
+ + = + +
+
= = +
−
ω ω
ω
οο
ο
• Common implementation C1 = C2 = C, R3 = R, R4 = R / m
m Q CRQ
o
= =422
ω
• A common implementation of the single amplifier biquad is the Salen -key filter
• A low - pass filter can be seen below
• Similar circuits are available for the other filter configurations
ω c R C CQ C
C= =1
0 52 1 2
1
2.
Sensitivity• Because of telerances in component values and because of the finite
opamp gain the response of the actual filter will deviate from theideal response
• As a means of predicting such deviations, the filter designeremploys the concept of sensitivity
• For second order filters one is normally interested in finding howsensitive their poles are relative to variations (Both initial tolerancesand future changes) in RC component values and amplifier gain
• These sensitivities can be quantified using the classical sensitivityfunction
S
yy
xx
yx
xyx
y
x= =
→lim
∆
∆
∆0
∂∂
• Here x denotes the value of a component and y denotes a circuitparameter of interest (e.g. ωo, Q). For small changes
S
yy
xx
xy =
∆
∆
Thus we use the value of Sxy to determine the per unit change in y
due to a given per - unit change in x
• If the sensitivity of Q relative to a particular resistance R1 is 5, thena 1% increase in R1 results in a 5% increase in the value of Q
Switched - Capacitor Filters
• Active RC filters are difficult to implement totally on an IC due tothe requirements of large - valued capacitors and accurate RC timeconstants
• The switched capacitor filter technique is based on the realizationthat a capacitor switched between two circuit nodes at a sufficientlyhigh rate is equivalent to a resistor connecting these two nodes
Consider the Following Circuit
• From the above circuit we see that during each clock period TC anamount of charge qC1 = C1 v1 is subtracted from the input sourceand supplied to the integrator capacitor C2
• The average current flow between the input node and virtual ground(VG) is
iC vTAV
i
C
= 1
If TC is sufficiently short one can think of the process as continuous and define an equivalent resistance REQ that is in effective resistance between nodes IN and VG
R vi
TCEQ
i
AV
C= =1
The time constant for the integrator is:
Time constant = =C R TCCEQ C2
2
1
• Thus the time constant that determines the frequency response of thefilter is determined by the clock period TC and the capacitor ratio C2 / C1.Both of these parameters can be well controlled in an IC process
• Note the dependence on capacitor ratio rather than absolute value. Theaccuracy of capacitor ratios in MOS technology are on the order of 0.1%
• For reasonable clock frequencies (100 kHz) and not too large capacitorratios (10) one can obtain relatively large time constants (10-4 s)
• Switched capacitor filter ICs offer a low cost high order filter on a singleIC
• The clock frequency must be higher than any frequency component ofthe signal (typically 100x)
• Can be easily programmed by changing the clock frequency
• Some of clock signal feeds through to the output, signals near the clockfrequency can be aliased into the passband, overall increase in the noisefloor
Oscillators and Waveform Shaping Circuits
• In the design of electronic systems the need frequently arises forsignals having prescribed waveforms (e.g. sinusoidal, square, triangle,pulse, etc.)
• Commonly used in computers, control systems, communicationsystems and test and measurement systems
• Two common ways for generating sinusoids
– Positive feedback loop with non-linear gain limiting mechanism
– Appropriately shaping other waveforms such as triangle waves
• Circuits that directly generate square, triangle and pulse waveformsgenerally employ circuit blocks known as multivibrators. Three basictypes are bistable, astable and monostable
Sinusoidal Oscillators
• Commonly referred to as linear sine-wave oscillators although someform of non-linearity has to be employed to limit the output amplitude
• Analysis of circuits is more difficult as s - plane analysis cannot bedirectly applied to the non-linear part of the circuit
• The basic structure of a sinusoidal oscillator consists of an amplifierand a frequency selective network connected in a positive feedbackloop
• In actual oscillator no input will be present, included to help explainoperation
• Note the feedback signal XF is summed with a positive sign
A sA s
A s sf ( )( )
( ) ( )=
−1 β
The loop gain is
L s A s s( ) ( ) ( )= β
and the characteristic equation is
1 0− =L s( )
• If at a specific frequency fo the loop gain Aβ is equal to unity itfollows that Af will be infinite. Such a circuit is by definition anoscillator
• Thus for sinusoidal oscillation at ωo
L j A j j( ) ( ) ( )ω ω β ωο ο ο= = 1 Barkhausen Criteria
• Unity gain, zero phase shift
Active Filter Based on Two Loop Integrator(Biquad)
• Opamp - RC circuit that realizes second order filter functions basedon the use of two integrators connected in cascade in an overallfeedback loop
• Consider second order high pass filter
T sV
Vk s
s s Q
hp
i
( ) = =+
+
2
2 2ω ωοο
where k is the high frequency gain. Rearranging the equation gives
VQ s
Vs
V kV
sV V
sV
V kVQ s
Vs
V
hp hp hp i
hp
hp
hp i hp hp
+
+
=
= − −
1
1
2
2
2
2
2
2
ω ω
ω
ω
ω
ω ω
ο ο
ο
ο
ο
ο ο
The signal can be obtained by passing through
an integrator with a time constant equal to 1 . Passing
the resulting signal through another identical integrator
generates
hp
• The signal at the output of the first integrator is
−
−
= −+
+
=
ω
ωω
ω ω
ο
ο
ο
οο
s V
V
s V
V
k s
s s Q
T s
hp
i
hp
ibp
which is a bandpass function
2 2( )
• Similarly the output of the second integrator is a low pass function
ωω
ω ω
ο
ο
οο
2
2 2
2 2
sV
V
k
s s Q
T shp
ilp
=+
= ( )
• The two - integrator - loop biquad realizes three basic second orderfilter functions LP, BP and HP simultaneously. This circuit iscommonly called the universal active filter
• If Rf / R = 1
CR RR Q k Q= = − = −
1 2 1 2 13
2ω ο
By summing the LP, BP, and HP outputs the overall transfer function of the KHN biquad and summer is
VV
k RR s s R
RR
R
s s Q
o
i
F
H
F
B
F
L= −
−
+
+
+
2 2
2 2
ω ω
ω ω
ο ο
οο
• An alternative two - loop integrator which uses three opamps insingle ended mode is the Tow - Thomas biquad. Details can befound on pages 804 & 805 of the text
• Although Two - Integrator loop biquads are versatile and easy todesign, their performance is adversly affected by the finitebandwidth of the opamps
Single Amplifier Biquad Filters
• Second order filter functions can also be implemented with a singleamplifier. These minimal realizations are low power and low cost,however, they suffer from greater dependence on opamp gain andbandwidth and are generally more sensitive to tolerances in theresistors and capacitors
• The single amplifier biquads (SABs) are therefore generally limited toless stringent filter specifications (Q < 10)
Active Filters
• In this section we study a family of opamp - RC circuits that realizethe various second order filter functions by replacing the inductor L inthe LCR resonator with an opamp - RC circuit that has an inductiveinput impedance
• Many opamp - RC circuits have been proposed for simulating theoperation of an inductor
• One of the simplest is the negative impedance converter (NIC)
• Can be used to convert a capacitor to a “backward” inductor
Zj C
I v j C
ZvI
vv j C j C
jC
C
C IN IN
ININ
IN
IN
IN
= = −
= =−
= − =
1
1
1
ωω
ω ω ω
ωEquivalent to an inductor of value
• One of the best circuits for simulating an inductor is the Antoniouinductance simulation circuit. This circuit is very tolerant to thenon-ideal properties of opamps
• The circuit is shown below
The effective inductance of the circuit is
Typically
LC R R R
R
R R R R R
C C
L C R
=
= = = ==
=
4 1 3 5
2
1 2 3 5
4
2
Opamp - RC Resonator
ω
ω
ω
ο
ο
ο
= =
= =
= = = = = =
= =
1 1
1
6 4 6 1 3 5
2
6 6 66
4
2
1 3 5
4 6 1 2 3 5
6
LC C C R R RR
Q C R RC
C
R
R R R
C C C R R R R R
CR Q RR
If
Second Order Functions The general second order (biquadratic) filter transfer function is given by
T sa s a s a
sQ
s
o( ) =+ +
+
+
22
1
2 2ω ωοο
where ωo and Q determine the poles according to
P PQ
jQ
o1 2 21 1
4, =
−± −
ω ωο
we are usually interested in the case of complex conjugate poles obtained for Q > 0.5
• The radial distance of the poles from the origin is the pole frequency
• The higher the value of Q the closer the poles are to the jω axis and themore selective (higher peak and initial rolloff) the filter responsebecomes
• An infinite value of Q locates the poles on the jω axis and can yieldsustained oscillations
• Q is called the pole quality factor
Second Order LCR Resonator
V
I YsL sC R
sC
s s CR LC
s s Q
LC Q CR LCQ C R
o
oo
o
= =
+ +
=+
+
+
+
= = = =
1 1
1 1 1 1
1 1 1
2
2 2
2
Equating the denominator to standard form gives
ω ω
ωω
ω ωοο
ο